Shift register unit using clock signals, gate drive circuit, display panel, display device and driving method

ABSTRACT

A shift register unit, a gate driving circuit, a display device, and a driving method are disclosed. The shift register unit includes a first sub-unit and a leakage prevention circuit; the first sub-unit includes a first input circuit and a first output circuit. The first input circuit controls a level of a first node in response to a first input signal, the first output circuit provides an output signal at an output terminal under control of the level of the first node, the leakage prevention circuit is connected to the first node and a first voltage terminal, and controls a level of a leakage prevention node under control of the level of the first node, whereby a conductive path is formed between the leakage prevention node and the first voltage terminal, and a circuit connected between the first node and the leakage prevention node is turned off.

The present application claims the priority of Chinese patent application No. 201910049743.0 filed on Jan. 18, 2019, and the entire disclosure of the aforementioned application is incorporated by reference as part of the disclosure of this application.

TECHNICAL FIELD

Embodiments of the present disclosure relate to a shift register unit, a gate driving circuit, a display device, and a driving method.

BACKGROUND

In the display field, especially in an OLED (organic light-emitting diode) display panel, a gate driving circuit is generally integrated in a GATE IC. The area of a chip in IC design is a main factor affecting the cost of the chip, and technology developers need to focus on how to effectively reduce the area of the chip.

SUMMARY

At least an embodiment of the present disclosure provides a shift register unit, comprising a first sub-unit and a leakage prevention circuit, and the first sub-unit comprises a first input circuit and a first output circuit. The first input circuit is configured to control a level of a first node in response to a first input signal, the first output circuit is configured to provide an output signal at an output terminal under control of the level of the first node, the leakage prevention circuit is connected to the first node and a first voltage terminal, and is configured to control a level of a leakage prevention node under control of the level of the first node, so as to form a conductive path between the leakage prevention node and the first voltage terminal and turn off a circuit connected between the first node and the leakage prevention node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the leakage prevention circuit comprises a first leakage prevention sub-circuit and a second leakage prevention sub-circuit. The first leakage prevention sub-circuit is connected to the first node and the leakage prevention node, and is configured to control the level of the leakage prevention node under control of the level of the first node, the second leakage prevention sub-circuit is connected to the leakage prevention node and the first voltage terminal, and the second leakage prevention sub-circuit is configured to form the conductive path between the leakage prevention node and the first voltage terminal under control of the level of the leakage prevention node or the level of the first node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first leakage prevention sub-circuit comprises a first leakage prevention transistor, and the second leakage prevention sub-circuit comprises a second leakage prevention transistor; a gate electrode of the first leakage prevention transistor is connected to the first node, a first electrode of the first leakage prevention transistor is configured to receive a second voltage, and a second electrode of the first leakage prevention transistor is connected to the leakage prevention node; and a gate electrode of the second leakage prevention transistor and a first electrode of the second leakage prevention transistor are configured to be connected to the leakage prevention node, and a second electrode of the second leakage prevention transistor is configured to be connected to the first voltage terminal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first leakage prevention sub-circuit comprises a first leakage prevention transistor, and the second leakage prevention sub-circuit comprises a third leakage prevention transistor; a gate electrode of the first leakage prevention transistor is connected to the first node, a first electrode of the first leakage prevention transistor is configured to receive a second voltage, and a second electrode of the first leakage prevention transistor is connected to the leakage prevention node; and a gate electrode of the third leakage prevention transistor is connected to the first node, a first electrode of the third leakage prevention transistor is connected to the leakage prevention node, and a second electrode of the third leakage prevention transistor is configured to be connected to the first voltage terminal.

For example, the shift register unit provided by an embodiment of the present disclosure further comprises a blanking input sub-unit, the blanking input sub-unit is connected to the first node, and is configured to receive a selection control signal and control the level of the first node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the blanking input sub-unit comprises a selection control circuit, a third input circuit, and a first transmission circuit; the selection control circuit is configured to control a level of a third node using the second input signal in response to the selection control signal, and maintain the level of the third node; the third input circuit is configured to transmit a first clock signal to a fourth node under control of the level of the third node; and the first transmission circuit is electrically connected to the first node, the fourth node, and the leakage prevention node, and is configured to control the level of the first node and the level of the leakage prevention node in respond to the first clock signal.

For example, the shift register unit provided by an embodiment of the present disclosure further comprises a second sub-unit, the second sub-unit comprises a second input circuit and a second output circuit, the second input circuit is configured to control a level of a second node in response to the first input signal, and the second output circuit is configured to output a second output signal under control of the level of the second node; and the blanking input sub-unit further comprises a second transmission circuit, and the second transmission circuit is electrically connected to the second node and the leakage prevention node, and is configured to transmit the level of the leakage prevention node to the second node in respond to the first clock signal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first transmission circuit comprises a first transmission transistor and a second transmission transistor, and the second transmission circuit comprises a third transmission transistor; a gate electrode of the first transmission transistor is configured to receive the first clock signal, a first electrode of the first transmission transistor is connected to the fourth node, and a second electrode of the first transmission transistor is connected to the leakage prevention node; a gate electrode of the second transmission transistor is configured to receive the first clock signal, a first electrode of the second transmission transistor is connected to the leakage prevention node, and a second electrode of the second transmission transistor is connected to the first node; and a gate electrode of the third transmission transistor is configured to receive the first clock signal, a first electrode of the third transmission transistor is connected to the leakage prevention node, and a second electrode of the third transmission transistor is connected to the second node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first input circuit comprises a first input transistor and a second input transistor, and the second input circuit comprises a third input transistor; a gate electrode of the first input transistor and a first electrode of the first input transistor are configured to receive the first input signal, and a second electrode of the first input transistor is connected to the leakage prevention node; a gate electrode of the second input transistor is configured to receive the first input signal, a first electrode of the second input transistor is connected to the leakage prevention node, and a second electrode of the second input transistor is connected to the first node; a gate electrode of the third input transistor is configured to receive the first input signal, a first electrode of the third input transistor is connected to the leakage prevention node, and a second electrode of the third input transistor is connected to the second node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the second input circuit further comprises a fourth input transistor, a gate electrode of the fourth input transistor and a first electrode of the fourth input transistor are configured to receive the first input signal, and a second electrode of the fourth input transistor is connected to the leakage prevention node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first sub-unit further comprises a first control circuit, a first reset circuit, a second reset circuit, a shift signal output terminal, and a first output signal terminal; the second sub-unit further comprises a second control circuit, a third reset circuit, a fourth reset circuit, and a second output signal terminal; the output signal comprises a shift signal and a first output signal, the output terminal comprises the shift signal output terminal and the first output signal terminal, the shift signal output terminal is configured to output the shift signal, and the first output signal terminal is configured to output the first output signal; the second output signal terminal is configured to output the second output signal; the first control circuit is configured to control a level of a fifth node under control of both the level of the first node and a third voltage; the first reset circuit is configured to reset the first node, the shift signal output terminal, and the first output signal terminal under control of the level of the fifth node; the second reset circuit is configured to reset the first node, the shift signal output terminal, and the first output signal terminal under control of a level of a sixth node; the second control circuit is configured to control the level of the sixth node under control of both the level of the second node and a fourth voltage; the third reset circuit is configured to reset the second node and the second output signal terminal under control of the level of the sixth node; and the fourth reset circuit is configured to reset the second node and the second output signal terminal under control of the level of the fifth node.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first sub-unit further comprises a third control circuit, a fourth control circuit, and a common control circuit, and the second sub-unit further comprises a fifth control circuit and a sixth control circuit; the third control circuit is connected to the fifth node and a common control node, and is configured to, in response to the first clock signal, enable the fifth node to be electrically connected to the common control node; the common control circuit is electrically connected to the common control node and the first voltage terminal, and is configured to, under control of the level of the third node, enable the common control node to be electrically connected to the first voltage terminal; the fourth control circuit is electrically connected to the fifth node and the first voltage terminal, and is configured to control the level of the fifth node in response to the first input signal; the fifth control circuit is connected to the sixth node and the common control node, and is configured to, in response to the first clock signal, enable the sixth node is electrically connect to the common control node; and the sixth control circuit is electrically connected to the sixth node and the first voltage terminal, and is configured to control the level of the sixth node in response to the first input signal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the third control circuit comprises a first control transistor, the fourth control circuit comprises a second control transistor, the common control circuit comprises a third control transistor, the fifth control circuit comprises a fourth control transistor, and the sixth control circuit comprises a fifth control transistor; a gate electrode of the first control transistor is configured to receive the first clock signal, a first electrode of the first control transistor is connected to the fifth node, and a second electrode of the first control transistor is connected to the common control node; a gate electrode of the second control transistor is configured to receive the first input signal, a first electrode of the second control transistor is connected to the fifth node, and a second electrode of the second control transistor is connected to the first voltage terminal; a gate electrode of the third control transistor is connected to the third node, a first electrode of the third control transistor is connected to the common control node, and a second electrode of the third control transistor is connected to the first voltage terminal; a gate electrode of the fourth control transistor is configured to receive the first clock signal, a first electrode of the fourth control transistor is connected to the sixth node, and a second electrode of the fourth control transistor is connected to the common control node; and a gate electrode of the fifth control transistor is configured to receive the first input signal, a first electrode of the fifth control transistor is connected to the sixth node, and a second electrode of the fifth control transistor is connected to the first voltage terminal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first sub-unit further comprises a third control circuit, a fourth control circuit, and a common control circuit, and the second sub-unit further comprises a fifth control circuit and a sixth control circuit; the third control circuit is connected to the third node, the fifth node, and a common control node, and is configured to, under control of the level of the third node, enable the fifth node to be electrically connected to the common control node; the common control circuit is electrically connected to the common control node and the first voltage terminal, and is configured to, in response to the first clock signal, enable the common control node to be electrically connected to the first voltage terminal; the fourth control circuit is electrically connected to the fifth node and the first voltage terminal, and is configured to control the level of the fifth node in response to the first input signal; the fifth control circuit is connected to the third node, the sixth node, and the common control node, and is configured to, under control of the level of the third node, enable the sixth node is electrically connect to the common control node; and the sixth control circuit is electrically connected to the sixth node and the first voltage terminal, and is configured to control the level of the sixth node in response to the first input signal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the third control circuit comprises a sixth control transistor, the fourth control circuit comprises a second control transistor, the common control circuit comprises a seventh control transistor, the fifth control circuit comprises an eighth control transistor, and the sixth control circuit comprises a fifth control transistor; a gate electrode of the sixth control transistor is connected to the third node, a first electrode of the sixth control transistor is connected to the fifth node, and a second electrode of the sixth control transistor is connected to the common control node; a gate electrode of the second control transistor is configured to receive the first input signal, a first electrode of the second control transistor is connected to the fifth node, and a second electrode of the second control transistor is connected to the first voltage terminal; a gate electrode of the seventh control transistor is configured to receive the first clock signal, a first electrode of the seventh control transistor is connected to the common control node, and a second electrode of the seventh control transistor is connected to the first voltage terminal; a gate electrode of the eighth control transistor is connected to the third node, a first electrode of the eighth control transistor is connected to the sixth node, and a second electrode of the eighth control transistor is connected to the common control node; and a gate electrode of the fifth control transistor is configured to receive the first input signal, a first electrode of the fifth control transistor is connected to the sixth node, and a second electrode of the fifth control transistor is connected to the first voltage terminal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the first sub-unit further comprises a fifth reset circuit and a sixth reset circuit, and the second sub-unit further comprises a seventh reset circuit and an eighth reset circuit; the fifth reset circuit is connected to the first node and the leakage prevention node, and is configured to reset the first node in response to a display reset signal, and the sixth reset circuit is connected to the first node and the leakage prevention node, and is configured to reset the first node in response to a total reset signal; and the seventh reset circuit is connected to the second node and the leakage prevention node, and is configured to reset the second node in response to the display reset signal, and the eighth reset circuit is connected to the second node and the leakage prevention node, and is configured to reset the second node in response to the total reset signal.

For example, in the shift register unit provided by an embodiment of the present disclosure, the fifth reset circuit comprises a first reset transistor, the sixth reset circuit comprises a second reset transistor, the seventh reset circuit comprises a third reset transistor, and the eighth reset circuit comprises a fourth reset transistor; a gate electrode of the first reset transistor is configured to receive the display reset signal, a first electrode of the first reset transistor is connected to the first node, and a second electrode of the first reset transistor is connected to the leakage prevention node; a gate electrode of the second reset transistor is configured to receive the total reset signal, a first electrode of the second reset transistor is connected to the first node, and a second electrode of the second reset transistor is connected to the leakage prevention node; a gate electrode of the third reset transistor is configured to receive the display reset signal, a first electrode of the third reset transistor is connected to the second node, and a second electrode of the third reset transistor is connected to the leakage prevention node; and a gate electrode of the fourth reset transistor is configured to receive the total reset signal, a first electrode of the fourth reset transistor is connected to the second node, and a second electrode of the fourth reset transistor is connected to the leakage prevention node.

At least an embodiment of the present disclosure provides a gate driving circuit, comprising a plurality of cascaded shift register units each of which is the shift register unit according to any one of the embodiments of the present disclosure.

At least an embodiment of the present disclosure provides a display device, comprising the gate driving circuit according to any one of the embodiments of the present disclosure.

At least an embodiment of the present disclosure provides a driving method for the shift register unit, comprising causing the leakage prevention circuit to control the level of the leakage prevention node under control of the level of the first node, causing the conductive path to be formed between the leakage prevention node and the first voltage terminal, and causing the circuit connected between the first node and the leakage prevention node to be turned off.

BRIEF DESCRIPTION OF THE DRAWINGS

In order to clearly illustrate the technical solution of the embodiments of the present disclosure, the drawings of the embodiments will be briefly described in the following. It is obvious that the described drawings in the following are only related to some embodiments of the present disclosure and thus are not limitative of the present disclosure.

FIG. 1 is a schematic diagram of a shift register unit;

FIG. 2 is a schematic diagram of a shift register unit provided by some embodiments of the present disclosure;

FIG. 3 is a circuit diagram of a leakage prevention circuit provided by some embodiments of the present disclosure;

FIG. 4 is a circuit diagram of another leakage prevention circuit provided by some embodiments of the present disclosure;

FIG. 5 is a schematic diagram of another shift register unit provided by some embodiments of the present disclosure;

FIG. 6 is a schematic diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 7 is a schematic diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 8 is a circuit diagram of a blanking input sub-unit provided by some embodiments of the present disclosure;

FIG. 9A to FIG. 9D are circuit diagrams of four blanking input sub-units provided by some embodiments of the present disclosure;

FIG. 10 is a schematic diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 11 is a schematic diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 12 is a schematic diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 13 is a circuit diagram of a shift register unit provided by some embodiments of the present disclosure;

FIG. 14A to FIG. 14C are circuit diagrams of three first input circuits provided by some embodiments of the present disclosure;

FIG. 15 is a circuit diagram of another shift register unit provided by some embodiments of the present disclosure;

FIG. 16 is a circuit diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 17 is a circuit diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 18 is a circuit diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 19 is a circuit diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 20 is a circuit diagram of yet another shift register unit provided by some embodiments of the present disclosure;

FIG. 21 is a circuit diagram of still another shift register unit provided by some embodiments of the present disclosure;

FIG. 22 is a schematic diagram of a gate driving circuit provided by some embodiments of the present disclosure;

FIG. 23 is a signal timing diagram corresponding to the operation of the gate driving circuit illustrated in FIG. 22 provided by some embodiments of the present disclosure;

FIG. 24 is a schematic diagram of another gate driving circuit provided by some embodiments of the present disclosure;

FIG. 25 is a signal timing diagram corresponding to the operation of the gate driving circuit illustrated in FIG. 24 provided by some embodiments of the present disclosure; and

FIG. 26 is a schematic diagram of a display device provided by some embodiments of the present disclosure.

DETAILED DESCRIPTION

In order to make objects, technical details and advantages of the embodiments of the disclosure apparent, the technical solutions of the embodiments will be described in a clearly and fully understandable way in connection with the drawings related to the embodiments of the disclosure. Apparently, the described embodiments are just a part but not all of the embodiments of the disclosure. Based on the described embodiments herein, those skilled in the art can obtain other embodiment (s), without any inventive work, which should be within the scope of the disclosure.

Unless otherwise defined, all the technical and scientific terms used herein have the same meanings as commonly understood by one of ordinary skill in the art to which the present disclosure belongs. The terms “first,” “second,” etc., which are used in the description and the claims of the present application for disclosure, are not intended to indicate any sequence, amount or importance, but distinguish various components. Also, the terms such as “a,” “an,” etc., are not intended to limit the amount, but indicate the existence of at least one. The terms “comprise,” “comprising,” “include,” “including,” etc., are intended to specify that the elements or the objects stated before these terms encompass the elements or the objects and equivalents thereof listed after these terms, but do not preclude the other elements or objects. The phrases “connect”, “connected”, “coupled”, etc., are not intended to define a physical connection or mechanical connection, but may include an electrical connection, directly or indirectly. “On,” “under,” “right,” “left” and the like are only used to indicate relative position relationship, and when the position of the object which is described is changed, the relative position relationship may be changed accordingly.

In the embodiments of the present disclosure, for example, in the case where each circuit is implemented by N-type transistors, the term “pull-up” means charging a node or an electrode of a transistor to allow the absolute value of the level of the node or the electrode to be increased, so as to implement a corresponding operation (e.g., turn-on) of the transistor; and the term “pull-down” means discharging a node or an electrode of a transistor to allow the absolute value of the level of the node or the electrode to be reduced, so as to implement a corresponding operation (e.g., turn-off) of the transistor.

For another example, in the case where each circuit is implemented by P-type transistors, the term “pull-up” means discharging a node or an electrode of a transistor to allow the absolute value of the level of the node or the electrode to be reduced, so as to implement a corresponding operation (e.g., turn-on) of the transistor; and the term “pull-down” means charging a node or an electrode of a transistor to allow the absolute value of the level of the node or the electrode to be increased, so as to implement a corresponding operation (e.g., turn-off) of the transistor.

Moreover, the specific meanings of the terms “pull-up” and “pull-down” may further be accordingly adjusted based on the specific type of the transistor, as long as the transistor can be controlled to implement the corresponding switch function.

Currently, a gate driving circuit for OLED usually includes three sub-circuits, that is, a detecting circuit, a display circuit, and a connecting circuit (or a gate circuit) for outputting a composite pulse of the detecting circuit and the display circuit. The circuit structure of the gate driving circuit is extremely complicated and cannot satisfy the requirements for a high resolution and a narrow bezel of a display panel.

FIG. 1 illustrates a shift register unit, for example, the shift register unit includes an input circuit 610 and an output circuit 620. The input circuit 610 is configured to control the level of a first node Q1 in response to the first input signal STU1, and the output circuit 620 is configured to provide an output signal OUT at an output terminal under the control of the level of the first node Q1. For example, in the case where a plurality of shift register units as illustrated in FIG. 1 are cascaded, a gate driving circuit may be formed, and the gate driving circuit may be used to drive a display device to perform a display operation. For example, in the case where the level of the first node Q1 is a high level, the output circuit 620 can provide the output signal OUT under the control of the level of the first node Q1, for example, the output signal OUT may be provided to a row of pixel units in the display panel to drive the row of pixel units for display.

For example, in the shift register unit illustrated in FIG. 1, in order to enable the shift register unit work better, other circuits need to be provided to better control the level of the first node Q1, for example, one or more reset circuits connected to the first node Q1 are provided. For example, after the shift register unit finishes outputting the output signal OUT, a reset circuit is used to reset the level of the first node Q1. For example, this reset operation changes the level of the first node Q1 from a high level to a low level. For example, when the level of the first node Q1 is a high level, if the above reset circuit cannot be completely turned off, the first node Q1 may leak through one or more of these reset circuits, that is, the first node Q1 may leak through the leakage path indicated by the dashed line in FIG. 1, which may cause the level of the first node Q1 cannot be maintained at a higher level when the output circuit 620 performs output, which may result in deviation of the output signal OUT, thus causing the display panel adopting the gate driving circuit formed by the shift register unit to display poorly.

It should be noted that, in some embodiments of the present disclosure, a circuit path, which is connected to the first node Q1, that may cause leakage of the first node Q1 is called a leakage path, and the leakage path may include one or more circuits (or sub-circuits), for example, includes a reset circuit that performs a reset operation on the first node Q1, and the following embodiments are the same and will not be described in detail.

In response to the above problem of leakage, at least one embodiment of the present disclosure provides a shift register unit, the shift register unit includes a first sub-unit and a leakage prevention circuit, and the first sub-unit includes a first input circuit and a first output circuit. The first input circuit is configured to control a level of a first node in response to a first input signal, the first output circuit is configured to provide an output signal at an output terminal under control of the level of the first node, and the leakage prevention circuit is connected to the first node and a first voltage terminal, and is configured to control a level of a leakage prevention node under control of the level of the first node, so as to form a conductive path between the leakage prevention node and the first voltage terminal and turn off a circuit connected between the first node and the leakage prevention node.

Some embodiments of the present disclosure further provide a gate driving circuit, a display device, and a driving method corresponding to the above shift register unit.

The shift register unit, the gate driving circuit, the display device and the driving method provided by some embodiments of the present disclosure can avoid the leakage of the first node, and avoid the problem of poor display of the display device adopting the gate driving circuit formed by the shift register unit. In addition, some embodiments of the present disclosure can also simplify the circuit structure, so that the bezel size of the display device adopting the gate driving circuit may be reduced, and the PPI of the display device may be improved.

In the following, the embodiments of the present disclosure and the examples thereof are described in detail with reference to the accompanying drawings.

At least one embodiment of the present disclosure provides a shift register unit 10, as illustrated in FIG. 2, the shift register unit 10 includes a first sub-unit 100 and a leakage prevention circuit 400, and the first sub-unit 100 includes a first input circuit 110 and a first output circuit 120. A plurality of the shift register units 10 may be cascaded to form a gate driving circuit provided by an embodiment of the present disclosure, and the gate driving circuit may be used for a display device to provide scan signals during the display process of one frame of the display device.

The first input circuit 110 is configured to control the level of a first node Q1 in response to a first input signal STU1, for example, to charge the first node Q1. For example, the first input circuit 110 may be configured to receive the first input signal STU1 and a second voltage VDD, the first input circuit 110 is turned on in response to the first input signal STU1, so that the first node Q1 can be charged using the second voltage VDD. For another example, the first input circuit 110 may not receive the second voltage VDD, and directly charge the first node Q1 using the first input signal STU1.

It should be noted that, in some embodiments of the present disclosure, the second voltage VDD is, for example, at a high level, and the following embodiments are the same and will not be described in detail.

The first output circuit 120 is configured to provide an output signal at an output terminal under the control of the level of the first node Q1. For example, as illustrated in FIG. 2, in some embodiments, the output signal includes a shift signal CR and a first output signal OUT1. For example, the first output circuit 120 may be configured to receive a second clock signal CLKB and a third clock signal CLKC, and when the first output circuit 120 is turned on under the control of the level of the first node Q1, the second clock signal CLKB is output as the shift signal CR, and the third clock signal CLKC is output as the first output signal OUT1.

For example, in a display period of one frame, the shift signal CR output by the first output circuit 120 may be provided to other shift register unit 10 as the first input signal STU1, thereby completing the progressive shift of the display scanning. The first output signal OUT1 output by the first output circuit 120 can drive a row of sub-pixel units in the display panel to perform the display scanning.

For example, in the case where a plurality of the shift register units 10 are cascaded to form a gate driving circuit, some of the shift register units 10 may be connected to a clock signal line to receive the first input signal STU1 provided by the clock signal line; alternatively, some of the shift register units 10 may also receive the shift signal CR output by the shift register unit 10 of other stage as the first input signal STU1.

It should be noted that, during the display period of one frame, the signal waveforms of the shift signal CR and the first output signal OUT1 output by the first output circuit 120 may be the same or different, which is not limited in the embodiments of the present disclosure.

As illustrated in FIG. 2, the leakage prevention circuit 400 is connected to the first node Q1 and a first voltage terminal VGL1, and is configured to control a level of a leakage prevention node OF under the control of the level of the first node Q1, so that a conductive path is formed between the leakage prevention node OF and the first voltage terminal VGL1, and the circuit (circuits) connected between the first node Q1 and the leakage prevention node OF is (are) turned off.

For example, in some embodiments, as illustrated in FIG. 2, the leakage prevention circuit 400 includes a first leakage prevention sub-circuit 410 and a second leakage prevention sub-circuit 420.

For example, the first leakage prevention sub-circuit 410 is connected to the first node Q1 and the leakage prevention node OF, and is configured to control the level of the leakage prevention node OF under the control of the level of the first node Q1. For example, the first leakage prevention sub-circuit 410 may be configured to receive the second voltage VDD, and the first leakage prevention sub-circuit, under the control of the level of the first node Q1, uses the second voltage VDD to control the level of the leakage prevention node OF.

For example, the second leakage prevention sub-circuit 420 is connected to the leakage prevention node OF and the first voltage terminal VGL1. The second leakage prevention sub-circuit 420 is configured to form the conductive path between the leakage prevention node OF and the first voltage terminal VGL1 under the control of the level of the leakage prevention node OF or the level of the first node Q1. For example, in the embodiments of the present disclosure, the first voltage terminal VGL1 is configured to provide the first voltage. It should be noted that, in the embodiments of the present disclosure, the first voltage is, for example, at a low level, and the following embodiments are the same and will not be described in detail. For example, the first voltage terminal VGL1 may be configured to be grounded.

As illustrated in FIG. 2, in the shift register unit 10 provided by the embodiment of the present disclosure, for example, when the first node Q1 is at a high level, the first node Q1 may leak through the leakage path illustrated in FIG. 2, and the leakage path may be a reset circuit connected to the first node Q1. For example, in the case where the reset circuit is not required to work, a control terminal of the reset circuit may be caused to receive the low-level first voltage. For example, when the level of the first node Q1 is at a high level, the first leakage prevention sub-circuit 410 is turned on under the control of the level of the first node Q1, so that the level of the leakage prevention node OF becomes high. At the same time, the second leakage prevention sub-circuit 420 is turned on under the control of the high level of the leakage prevention node OF or the high level of the first node Q1, thereby forming a conductive path between the leakage prevention node OF and the first voltage terminal VGL1, and causing the level of the leakage prevention node OF to be higher than the first voltage provided by the first voltage terminal VGL1.

After the control of the leakage prevention circuit 400, the level of the leakage prevention node OF can be made higher than the first voltage, so that the circuit in the leakage path (for example, the reset circuit) is turned off under the control of the level of the leakage prevention node OF and the first voltage, that is, the circuit connected between the first node Q1 and the leakage prevention node OF is turned off, so that leakage of the first node Q1 through the leakage path can be avoided. In the shift register units 10 provided by some embodiments of the present disclosure, the circuit that may cause the leakage of the first node Q1 is made to be electrically connected to the leakage prevention node OF, so that the leakage of the first node Q1 can be avoided.

The shift register units 10 provided by some embodiments of the present disclosure can not only avoid the leakage of the first node Q1, but also avoid the leakage of the multiple circuits (for example, multiple reset circuits), which are connected to the first node Q1, by only providing one leakage prevention circuit 400, so that the circuit structure may be simplified, the bezel size of the display device adopting the shift register unit may be reduced, and the PPI of the display device may be improved.

In addition, it should be noted that in the embodiments of the present disclosure, the high level and the low level are described relatively. The high level represents a relatively higher voltage range (for example, the high level may adopt 5V, 10V, or other appropriate voltage), and multiple high levels may be same or different. Similarly, the low level represents a lower voltage range (for example, the low level may adopt 0V, −5V, −10V, or other appropriate voltage), and multiple low levels can be same or different. For example, the minimum value of the high level is greater than the maximum value of the low level.

It should be noted that, in the embodiments of the present disclosure, controlling a level of a node (for example, the first node Q1, the second node Q2, etc.) including charging the node to pull up the level of the node, or discharging the node to pull down the level of the node. For example, a capacitor may be set to be electrically connected to the node, and charging the node means charging the capacitor electrically connected to the node; similarly, discharging the node means discharging the capacitor electrically connected to the node.

In the shift register units 10 provided by some embodiments of the present disclosure, as illustrated in FIG. 3, the first leakage prevention sub-circuit 410 includes a first leakage prevention transistor A1, and the second leakage prevention sub-circuit 420 includes a second leakage prevention transistor A2. It should be noted that FIG. 3 and FIG. 4 only illustrate part of the circuits of the shift register unit 10.

The gate electrode of the first leakage prevention transistor A1 is connected to the first node Q1, the first electrode of the first leakage prevention transistor A1 is configured to receive the second voltage VDD, and the second electrode of the first leakage prevention transistor A1 is connected to the leakage prevention node OF. For example, when the level of the first node Q1 is a high level, the first leakage prevention transistor A1 is turned on, so that the level of the leakage prevention node OF may be controlled by the second voltage VDD, for example, the level of the leakage prevention node OF is caused to become high.

The gate electrode and the first electrode of the second leakage prevention transistor A2 are electrically connected to each other and are configured to be connected to the leakage prevention node OF, and the second electrode of the second leakage prevention transistor A2 is configured to be connected to the first voltage terminal VGL1 to receive the first voltage. As illustrated in FIG. 3, the second leakage prevention transistor A2 adopts a diode connection. When the leakage prevention node OF is at a high level, the second leakage prevention transistor A2 is turned on, in this case, the second leakage prevention transistor A2 has a unidirectional conduction characteristic, that is, the current direction is from the leakage prevention node OF to the first voltage terminal VGL1, and due to the internal resistance of the second leakage prevention transistor A2, the level of the leakage prevention node OF is greater than the first voltage provided by the first voltage terminal VGL1.

For example, as illustrated in FIG. 3, the shift register unit 10 further includes a first reset transistor R1 and a second reset transistor R2 that reset the first node Q1.

For example, the gate electrode of the first reset transistor R1 is configured to receive a display reset signal STD, and when the display reset signal STD is at a high level, the first reset transistor R1 is turned on, so that the first node Q1 is electrically connected to the first voltage terminal VGL1 through the first reset transistor R1 and the second leakage prevention transistor A2, and the first node Q1 may be reset using the low-level first voltage provided by the first voltage terminal VGL1.

For example, the gate electrode of the second reset transistor R2 is configured to receive a total reset signal TRST, and when the total reset signal TRST is at a high level, the second reset transistor R2 is turned on, so that the first node Q1 is electrically connected to the first voltage terminal VGL1 through the second reset transistor R2 and the second leakage prevention transistor A2, and the first node Q1 may be reset using the low-level first voltage provided by the first voltage terminal VGL1. It should be noted that the display reset signal STD and the total reset signal TRST will be described in detail below, and will not be repeated here.

For example, when the first node Q1 is at a high level, at this time, the display reset signal STD provided to the first reset transistor R1 and the total reset signal TRST provided to the second reset transistor R2 may be the low-level first voltage, so that the first reset transistor R1 and the second reset transistor R2 are turned off. If the first reset transistor R1 and the second reset transistor R2 cannot be completely turned off, the first node Q1 may leak through the first reset transistor R1 or the second reset transistor R2.

As illustrated in FIG. 3, by providing the first leakage prevention transistor A1 and the second leakage prevention transistor A2, when the level of the first node Q1 is a high level, the potential of the leakage prevention node OF is made to be higher than the first voltage, so that relative to the display reset signal STD or the total reset signal TRST with a predetermined low level (for example, the first voltage), the Vgs (voltage difference between the gate electrode and the source electrode) of the first reset transistor R1 and the Vgs of the second reset transistor R2 are both less than zero, so that both the first reset transistor R1 and the second reset transistor R2 are kept to be turned off. In addition, because the potential of the leakage prevention node OF becomes higher (higher than the first voltage), the voltage difference between the first node Q1 and the leakage prevention node OF becomes smaller (even negative), so that the first node Q1 cannot leak through the first reset transistor R1 or the second reset transistor R2, or the degree of the leakage may be reduced. It should be noted that, in FIG. 3, in order to explain the working principle of leakage prevention, regarding the possible leakage path of the first node Q1, only the first reset transistor R1 and the second reset transistor R2 are illustrated, and in the case where there are other circuits connected to the first node Q1, in order to avoid leakage of the first node Q1 through the circuits, as long as the circuit is connected to the leakage prevention node OF. That is, in the shift register units 10 provided by some embodiments of the present disclosure, by setting the first leakage prevention transistor A1 and the second leakage prevention transistor A2, when the first node Q1 is at a high level, the circuit connected between the first node Q1 and the leakage prevention node OF is turned off, so that the leakage of the first node Q1 can be avoided.

It should be noted that, in the embodiment illustrated in FIG. 3, when the first reset transistor R1 or the second reset transistor R2 resets the first node Q1, the effect of the second leakage prevention transistor A2 is no longer to prevent leakage but to reset, that is, the second leakage prevention transistor A2 is multiplexed as a reset transistor.

In other embodiments of the present disclosure, as illustrated in FIG. 4, the first leakage prevention sub-circuit 410 includes a first leakage prevention transistor A1, and the second leakage prevention sub-circuit 420 includes a third leakage prevention transistor A3.

For example, the gate electrode of the first leakage prevention transistor A1 is connected to the first node Q1, the first electrode of the first leakage prevention transistor A1 is configured to receive the second voltage VDD, and the second electrode of the first leakage prevention transistor A1 is connected to the leakage prevention node OF. For example, when the level of the first node Q1 is a high level, the first leakage prevention transistor A1 is turned on, so that the level of the leakage prevention node OF may be controlled by the second voltage VDD, for example, the level of the leakage prevention node OF is caused to become high.

For example, the gate electrode of the third leakage prevention transistor A3 is connected to the first node Q1, the first electrode of the third leakage prevention transistor A3 is connected to the leakage prevention node OF, and the second electrode of the third leakage prevention transistor A3 is configured to be connected to the first voltage terminal VGL1 to receive the first voltage. For example, when the first node Q1 is at a high level, the third leakage prevention transistor A3 is turned on, so that a conductive path is formed between the leakage prevention node OF and the first voltage terminal VGL1, and the level of the leakage prevention node OF is greater than the first voltage provided by the first voltage terminal VGL1.

In the shift register units 10 provided by some embodiments of the present disclosure, by setting the first leakage prevention transistor A1 and the third leakage prevention transistor A3, when the first node Q1 is at a high level, the level of the leakage prevention node OF is made to be higher, relative to the display reset signal STD or the total reset signal TRST with a predetermined low level (for example, the first voltage), so that, for example, both the first reset transistor R1 and the second reset transistor R2 are kept to be turned off, so that the circuit connected between the first node Q1 and the leakage prevention node OF is turned off. In addition, because the potential of the leakage prevention node OF becomes higher (higher than the first voltage), the voltage difference between the first node Q1 and the leakage prevention node OF becomes smaller (even negative), so that the leakage of the first node Q1 can be avoided, or the degree of the leakage may be reduced.

It should be noted that the transistors illustrated in FIG. 3 and FIG. 4 are described by taking N-type transistors as an example.

It should be noted that each of the transistors adopted in the embodiments of the present disclosure may be a thin film transistor, a field effect transistor or other switching component having the same characteristics. In the embodiments of the present disclosure, the thin film transistor is taken as an example for description. The source electrode and the drain electrode of the transistor used here may be structurally symmetrical, so that the source electrode and the drain electrode may be structurally indistinguishable. In the embodiments of the present disclosure, in order to distinguish the two electrodes of the transistor except the gate electrode, one electrode is directly described as the first electrode, and the other electrode is described as the second electrode. In addition, the transistors can be divided into N-type and P-type transistors according to the characteristics of the transistors. In the case where the transistor is the N-type transistor, the turn-on voltage is a high-level voltage (e.g., 5V, 10V, or other suitable voltage), and the turn-off voltage is a low-level voltage (e.g., 0V, −5V, −10V, or other suitable voltage). The transistors in the following embodiments are also described using N-type transistors as an example, and will not be described in detail. However, the embodiments of the present disclosure include but are not limited thereto. For example, one or more transistors in the shift register unit provided by the embodiments of the present disclosure may also adopt P-type transistors. In the case where the transistor is the P-type transistor, the turn-on voltage is a low-level voltage (for example, 0V, −5V, −10V or other suitable voltage), and the turn-off voltage is a high-level voltage (for example, 5V, 10V or other suitable voltage).

When compensating a sub-pixel unit in the OLED display panel, in addition to setting a pixel compensation circuit in the sub-pixel unit for internal compensation, external compensation may also be performed by setting a sensing transistor. When the external compensation is performed, the gate driving circuit formed by the shift register units needs to provide the sub-pixel unit in the display panel with a driving signal for a scanning transistor and a driving signal for the sensing transistor, respectively. For example, the gate driving circuit provides a scan driving signal for the scanning transistor in a display period of one frame, and provides a sense driving signal for the sensing transistor in a blanking period of one frame.

In an external compensation method, the sense driving signal output by the gate driving circuit is sequentially scanned line by line. For example, the sense driving signal for the first row of the sub-pixel units in the display panel is output during the blanking period of the first frame, the sense driving signal for the second row of the sub-pixel units in the display panel is output during the blanking period of the second frame, and so on, the sense driving signal is sequentially output line by line in the frequency of that the sense driving signal corresponding to one row of sub-pixel units is output during each frame, that is, the progressive sequence compensation of the display panel is completed.

However, in the case where the above progressive sequence compensation method is performed, the problem of poor display may occur: one is that there is a scanning line that moves line by line during the display scanning process of multiple frames; the other one is that the difference of time points for the external compensation may cause the difference of brightness in different regions of the display panel to be large. For example, when performing the external compensation on the 100th row of the sub-pixel units in the display panel, although the 10th row of the sub-pixel units in the display panel has been performed the external compensation, however, at this time, the light-emission brightness of the 10th row of the sub-pixel units may have changed, for example, the light-emission brightness is reduced, which may cause uneven brightness in different regions of the display panel, and this problem is more obvious in large-size display panels.

As described above, in the case where the gate driving circuit drives a display panel, in order to implement the external compensation, the gate driving circuit needs to not only output the scan driving signal for the display period, but also output the sense driving signal for the blanking period.

It should be noted that, in some embodiments of the present disclosure, the random compensation refers to an external compensation method that is different from the progressive sequence compensation, that is, the sense driving signal corresponding to any one row of the sub-pixel units in the display panel is output randomly during the blanking period of a frame, and the following embodiments are the same and will not be described in detail.

In addition, in some embodiments of the present disclosure, for the purpose of description, the term “one frame”, “each frame” or “a frame” includes a display period and a blanking period which are sequentially performed. For example, in the display period, the gate driving circuit outputs a driving signal, and the driving signal can drive the display panel from the first row to the last row to perform a display scanning of one complete image; and in the blanking period, the gate driving circuit outputs a driving signal, and the driving signal can be used to drive sensing transistors in one row of sub-pixel units in the display panel to perform the external compensation on the sub-pixel units in the row.

In order to implement the above random compensation, as illustrated in FIG. 5, in some embodiments of the present disclosure, the shift register unit 10 further includes a blanking input sub-unit 300. The blanking input sub-unit 300 is connected to the first node Q1, and is configured to receive a selection control signal OE and control the level of the first node Q1, for example, to charge the first node Q1.

For example, in the blanking period of one frame, the blanking input sub-unit 300 may charge the first node Q1, so that the first output circuit 120 outputs the first output signal OUT1 under the control of the level of the first node Q1. The first output signal OUT1 may be used to drive the sensing transistors in a row of sub-pixel units in the display panel to complete the external compensation of the row of sub-pixel units.

The gate driving circuit and the display device adopting the shift register unit 10 provided by the embodiments of the present disclosure can implement the random compensation, thereby avoiding the problems of poor display such as the scanning lines and the uneven display brightness due to the progressive sequence compensation.

As illustrated in FIG. 6, in some embodiments of the present disclosure, the blanking input sub-unit 300 includes a selection control circuit 310, a third input circuit 320, and a first transmission circuit 330.

The selection control circuit 310 is configured to control the level of a third node H using a second input signal STU2 in response to the selection control signal OE, for example, charge the third node H and maintain the level of the third node H. For example, in the display period of one frame, the selection control circuit 310 may be turned on under the control of the selection control signal OE, thereby charging the third node H with the second input signal STU2. The level (e.g., a high level) of the third node H may be maintained from the display period of one frame to the blanking period of the frame.

For example, in the case where a plurality of shift register units 10 are cascaded to form the gate driving circuit, the shift register unit 10 of a certain stage may receive the shift signal CR output by the shift register unit 10 of the other stage as the second input signal STU2. For example, in the case where it is necessary to select the shift register unit 10 of a certain stage to output the driving signal in the blanking period of one frame, the waveform timings of the selection control signal OE and the second input signal STU2 provided to the shift register unit 10 of the stage can be made the same, so that the selection control circuit 310 in the shift register unit 10 of this stage is turned on.

The third input circuit 320 is configured to transmit a first clock signal CLKA to a fourth node N under the control of the level of the third node H. For example, the third input circuit 320 may be configured to receive the first clock signal CLKA. When the third input circuit 320 is turned on under the control of the level of the third node H, the first clock signal CLKA is transmitted to the fourth node N, thereby controlling the level of the fourth node N. For example, during the blanking period of one frame, when the first clock signal CLKA is at a high level, the third input circuit 320 may transmit the high level to the fourth node N, so that the level of the fourth node N is caused to become high.

The first transmission circuit 330 is electrically connected to the first node Q1, the fourth node N, and the leakage prevention node OF, and is configured to control the level of the first node Q1 and the level of the leakage prevention node OF in respond to the first clock signal CLKA. For example, in some embodiments, the first transmission circuit 330 may be configured to receive the first clock signal CLKA, and when the first transmission circuit 330 is turned on under the control of the first clock signal CLKA, the level of the fourth node N is transmitted to the first node Q1 to control the level of the first node Q1, for example, to charge the first node Q1. In addition, when the first transmission circuit 330 is turned on under the control of the first clock signal CLKA, the level of the fourth node N is also transmitted to the leakage prevention node OF, thereby controlling the level of the leakage prevention node OF.

It should be noted that, in the embodiments of the present disclosure, the blanking input sub-unit 300 is provided in the shift register unit 10 in order to implement that the driving signal can be output during the blanking period of one frame. “Blanking” in the blanking input sub-unit 300 only means that it is related to the blanking period in one frame, and does not limit that the blanking input sub-unit 300 only works in the blanking period. The following embodiments are the same and will not be described in detail.

As illustrated in FIG. 7, the shift register unit 10 provided by some embodiments of the present disclosure further includes a second sub-unit 200. The second sub-unit 200 includes a second input circuit 210 and a second output circuit 220.

The second input circuit 210 is configured to control the level of the second node Q2 in response to the first input signal STU1, for example, to charge the second node Q2. For example, the second input circuit 210 may be configured to receive the first input signal STU1 and the second voltage VDD, the second input circuit 210 is turned on in response to the first input signal STU1, thereby charging the second node Q2 using the second voltage VDD. For another example, the second input circuit 210 may not receive the second voltage VDD, and directly charges the second node Q2 using the first input signal STU1.

The second output circuit 220 is configured to output a second output signal OUT2 under the control of the level of the second node Q2. For example, the second output circuit 220 may be configured to receive a fourth clock signal CLKD, and when the second output circuit 220 is turned on under the control of the level of the first node Q1, the fourth clock signal CLKD may be output being as the second output signal OUT2.

The shift register unit 10 provided by the embodiment of the present disclosure can simultaneously charge a plurality of sub-units (the first sub-unit 100 and the second sub-unit 200, etc.), and only one sub-unit (for example, the first sub-unit 100) needs to output the shift signal, while other sub-units (such as the second sub-unit 200, etc.) do not need to output the shift signal, thereby saving the number of clock signal lines and transistors, and thus reducing the bezel size of the display device adopting the shift register unit 10, and improving the PPI of the display device.

It should be noted that FIG. 7 is only an example of the present disclosure, and the embodiments of the present disclosure do not limit the number of sub-units included in the shift register unit 10, for example, may include three, four, or more sub-units, and the number of sub-units can be set according to the actual situation.

In the case where the shift register unit 10 includes the second sub-unit 200, the blanking input sub-unit 300 further includes a second transmission circuit 340.

The second transmission circuit 340 is electrically connected to the second node Q2 and the leakage prevention node OF, and is configured to transmit the level of the leakage prevention node OF to the second node Q2 in response to the first clock signal CLKA. For example, in some embodiments, the second transmission circuit 340 may be configured to receive the first clock signal CLKA, and when the second transmission circuit 340 is turned on under the control of the first clock signal CLKA, the level of the leakage prevention node OF is transmitted to the second node Q2 to control the level of the second node Q2, for example, to charge the second node Q2.

For example, in the display period of one frame, the second output signal OUT2 output by the second output circuit 220 may drive a row of sub-pixel units in the display panel to perform display scanning. For another example, during the blanking period of one frame, the second output signal OUT2 output by the second output circuit 220 may be used to drive the sensing transistors in a row of sub-pixel units in the display panel to complete the external compensation of the row of sub-pixel units.

In the shift register units 10 provided by some embodiments of the present disclosure, the first transmission circuit 330 and the second transmission circuit 340 are electrically connected through the leakage prevention node OF. When the first transmission circuit 330 charges the first node Q1, the high level of the fourth node N may also be transmitted to the second node Q2 through the leakage prevention node OF, thereby implementing the charging of the second node Q2. In addition, because both the first transmission circuit 330 and the second transmission circuit 340 are electrically connected to the leakage prevention node OF, the leakage of the first node Q1 through the first transmission circuit 330 can be avoided, and the leakage of the second node Q2 through the second transmission circuit 340 can also be avoided.

In addition, in the case where the shift register unit 10 includes three, four, or more sub-units, accordingly, three, four, or more transmission circuits need to be provided to implement the function of the blanking input sub-unit 300.

In some embodiments of the present disclosure, in the case where the shift register unit 10 includes a plurality of sub-units (the first sub-unit 100 and the second sub-unit 200, etc.), these sub-units may share one blanking input sub-unit 300, so that the area occupied by the shift register unit 10 is reduced, and the bezel size of the display device adopting the shift register unit is reduced, thereby improving the PPI of the display device.

As illustrated in FIG. 8, and FIG. 9A to FIG. 9C, in some embodiments, the selection control circuit 310 may be implemented to include a fifth input transistor B5 and a first capacitor C1. The gate electrode of the fifth input transistor B5 is configured to receive the selection control signal OE, the first electrode of the fifth input transistor B5 is configured to receive the second input signal STU2, and the second electrode of the fifth input transistor B5 is connected to the third node H. For example, when the selection control signal OE is a high-level turn-on signal, the fifth input transistor B5 is turned on, so that the third node H may be charged using the second input signal STU2.

The first electrode of the first capacitor C1 is connected to the third node H, the second electrode of the first capacitor C1 is connected to the first voltage terminal VGL1 to receive the first voltage, or the second electrode of the first capacitor C1 is configured to receive the second voltage VDD. By providing the first capacitor C1, the potential of the third node H may be maintained. For example, in the display period of one frame, the selection control circuit 310 charges the third node H to pull up the third node H to a high potential, and the first capacitor C1 may maintain the high potential of the third node H until the blanking period of the frame.

For example, in the embodiment illustrated in FIG. 8, the third input circuit 320 may be implemented as the seventh input transistor B7. The gate electrode of the seventh input transistor B7 is connected to the third node H, the first electrode of the seventh input transistor B7 is configured to receive the first clock signal CLKA, and the second electrode of the seventh input transistor B7 is connected to the fourth node N. For example, when the third node H is at a high level, the seventh input transistor B7 is turned on, so that the first clock signal CLKA may be transmitted to the fourth node N to pull up the level of the fourth node N.

For example, in the embodiment illustrated in FIG. 8, the first transmission circuit 330 includes a first transmission transistor T1 and a second transmission transistor T2, and the second transmission circuit 340 includes a third transmission transistor T3.

The gate electrode of the first transmission transistor T1 is configured to receive the first clock signal CLKA, the first electrode of the first transmission transistor T1 is connected to the fourth node N, and the second electrode of the first transmission transistor T1 is connected to the leakage prevention node OF. The gate electrode of the second transmission transistor T2 is configured to receive the first clock signal CLKA, the first electrode of the second transmission transistor T2 is connected to the leakage prevention node OF, and the second electrode of the second transmission transistor T2 is connected to the first node Q1. The gate electrode of the third transmission transistor T3 is configured to receive the first clock signal CLKA, the first electrode of the third transmission transistor T3 is connected to the leakage prevention node OF, and the second electrode of the third transmission transistor T3 is connected to the second node Q2.

For example, when the first clock signal CLKA is at a high level, the first transmission transistor T1, the second transmission transistor T2, and the third transmission transistor T3 are all turned on, and the first transmission transistor T1 that is turned on may transmit the high level of the fourth node N to the leakage prevention node OF, so that the level of the leakage prevention node OF becomes a high level; then the second transmission transistor T2 that is turned on transmits the high level of the leakage prevention node OF to the first node Q1 to charge the first node Q1; the third transmission transistor T3 that is turned on transmits the high level of the leakage prevention node OF to the second node Q2 to charge the second node Q2. As described above, when charging the first node Q1 and the second node Q2, the first transmission transistor T1 is multiplexed. In addition, because the second transmission transistor T2 is connected to the leakage prevention node OF, the second transmission transistor T2 can also avoid the leakage of the first node Q1. Because the third transmission transistor T3 is connected to the leakage prevention node OF, the third transmission transistor T3 can also avoid the leakage of the second node Q2.

The blanking input sub-units 300 provided in FIG. 9A to FIG. 9C are described below. It should be noted that in the following description, the same parts of FIG. 9A to FIG. 9C and FIG. 8 will not be described in detail.

For example, as illustrated in FIG. 9A, relative to FIG. 8, the blanking input sub-unit 300 further includes a first coupling capacitor CST1. The first electrode of the first coupling capacitor CST1 is configured to receive the first clock signal CLKA, and the second electrode of the first coupling capacitor CST1 is connected to the third node H. For example, when the first clock signal CLKA changes from a low level to a high level, the first clock signal CLKA may pull up, by coupling, the third node H by the coupling effect of the first coupling capacitor CST1, the level of the third node H is further pulled up, so that the seventh input transistor B7 may be ensured to be turned on more sufficiently.

For example, as illustrated in FIG. 9B, relative to FIG. 9A, the blanking input sub-unit 300 further includes a second coupling capacitor CST2, the first electrode of the second coupling capacitor CST2 is connected to the third node H, and the second electrode of the second coupling capacitor CST2 is connected to the fourth node N. For example, when the first clock signal CLKA changes from a low level to a high level, if the seventh input transistor B7 is turned on at this time, the high-level first clock signal CLKA may be transmitted to the fourth node N through the seventh input transistor B7, so that the potential of the second electrode of the second coupling capacitor CST2 is pulled up, and the level of the third node H may further be pulled up by the bootstrap effect of the second coupling capacitor CST2, thereby ensuring the seventh input transistor B7 to be turned on more sufficiently.

For example, as illustrated in FIG. 9C, the first transmission circuit 330 includes a first transmission transistor T1 and a second transmission transistor T2, and the second transmission circuit 340 includes a third transmission transistor T3.

The gate electrode of the first transmission transistor T1 is connected to the fourth node N, the first electrode of the first transmission transistor T1 is configured to receive the high-level second voltage VDD, and the second electrode of the first transmission transistor T1 is connected to the leakage prevention node OF; the gate electrode of the second transmission transistor T2 is connected to the fourth node N, the first electrode of the second transmission transistor T2 is connected to the leakage prevention node OF, and the second electrode of the second transmission transistor T2 is connected to the first node Q1; The gate electrode of the third transmission transistor T3 is connected to the fourth node N, the first electrode of the third transmission transistor T3 is connected to the leakage prevention node OF, and the second electrode of the third transmission transistor T3 is connected to the second node Q2.

For example, when the first clock signal CLKA is at a high level, the high-level first clock signal CLKA is transmitted to the fourth node N through the seventh input transistor B7 that is turned on, so that the fourth node N becomes a high level, the first transmission transistor T1, the second transmission transistor T2, and the third transmission transistor T3 are all turned on, and the first transmission transistor T1 that is turned on may transmit the high-level second voltage VDD to the leakage prevention node OF, so that the level of the leakage prevention OF becomes a high level; then the second transmission transistor T2 that is turned on transmits the high level of the leakage prevention node OF to the first node Q1 to charge the first node Q1; the third transmission transistor T3 that is turned on transmits the high level of the leakage prevention node OF to the second node Q2 to charge the second node Q2.

For example, FIG. 9D also provides a blanking input sub-unit 300, relative to FIG. 9B, the selection control circuit 310 in the blanking input sub-unit 300 includes a sixth input transistor B6 in addition to the fifth input transistor B5, in addition, the blanking input sub-unit 300 further includes a fourth leakage prevention transistor A4.

As illustrated in FIG. 9D, the gate electrode of the fourth leakage prevention transistor A4 is connected to the third node H, the first electrode of the fourth leakage prevention transistor A4 is configured to receive the second voltage VDD, and the second electrode of the fourth leakage prevention transistor A4 is connected to the first electrode of the sixth input transistor B6, the gate electrode of the sixth input transistor B6 is configured to receive the selection control signal OE, and the second electrode of the sixth input transistor B6 is connected to the third node H.

The fourth leakage prevention transistor A4 and the sixth input transistor B6 cooperate to prevent the leakage of the third node H. For the working principle of preventing the leakage of the third node H, reference may be made to the corresponding description about the first node Q1, which is not repeated here.

As illustrated in FIG. 10, in the shift register units 10 provided by some embodiments of the present disclosure, the first sub-unit 100 further includes a first control circuit 130, a first reset circuit 140, a second reset circuit 150, a shift signal output terminal CRT, and a first output signal terminal OP1. The shift signal output terminal CRT is configured to output the shift signal CR, and the first output signal terminal OP1 is configured to output the first output signal OUT1.

The first control circuit 130 is configured to control the level of a fifth node QB_A under the control of the level of the first node Q1 and a third voltage VDD_A. For example, the first control circuit 130 is connected to the first node Q1 and the fifth node QB_A, and is configured to receive the third voltage VDD_A and the first voltage. For example, when the first node Q1 is at a high level, the first control circuit 130 may pull down the fifth node QB_A to a low level using the low-level first voltage. For another example, when the first node Q1 is at a low level, the first control circuit 130 may charge the fifth node QB_A using the third voltage VDD_A (for example, a high level) to pull up the fifth node QB_A to a high level.

The first reset circuit 140 is configured to reset the first node Q1, the shift signal output terminal CRT, and the first output signal terminal OP1 under the control of the level of the fifth node QB_A. For example, the first reset circuit 140 is connected to the first node Q1, the fifth node QB_A, the shift signal output terminal CRT, and the first output signal terminal OP1, and is configured to receive the first voltage and a fifth voltage VGL2. For example, when the first reset circuit 140 is turned on under the control of the level of the fifth node QB_A, the first node Q1 and the shift signal output terminal CRT may be pulled down and reset using the first voltage, and the first output signal terminal OP1 may be pulled down and reset using the fifth voltage VGL2. It should be noted that, in some embodiments of the present disclosure, the first output signal terminal OP1 may also be pulled down and reset using the first voltage, which is not limited in the present disclosure. In addition, in the embodiments of the present disclosure, the fifth voltage VGL2 is, for example, a low level, and the following embodiments are the same and will not be described in detail. In the embodiment of the present disclosure, the fifth voltage VGL2 may be the same as or different from the first voltage.

The second reset circuit 150 is configured to reset the first node Q1, the shift signal output terminal CRT, and the first output signal terminal OP1 under the control of the level of a sixth node QB_B. For example, the second reset circuit 150 is connected to the first node Q1, the sixth node QB_B, the shift signal output terminal CRT, and the first output signal terminal OP1, and is configured to receive the first voltage and the fifth voltage VGL2. For example, when the second reset circuit 150 is turned on under the control of the level of the sixth node QB_B, the first node Q1 and the shift signal output terminal CRT may be pulled down and reset using the first voltage, and the first output signal terminal OP1 may also be pulled down and reset using the fifth voltage VGL2.

As illustrated in FIG. 10, the second sub-unit 200 further includes a second control circuit 230, a third reset circuit 240, a fourth reset circuit 250, and a second output signal terminal OP2. The second output signal terminal OP2 is configured to output the second output signal OUT2.

The second control circuit 230 is configured to control the level of the sixth node QB_B under the control of the level of the second node Q2 and a fourth voltage VDD_B. For example, the second control circuit 230 is connected to the second node Q2 and the sixth node QB_B, and is configured to receive the fourth voltage VDD_B and the first voltage. For example, when the second node Q2 is at a high level, the second control circuit 230 may pull down the sixth node QB_B to a low level using the low-level first voltage. For another example, when the potential of the second node Q2 is at a low level, the second control circuit 230 may charge the sixth node QB_B using the fourth voltage VDD_B (for example, a high level) to pull up the sixth node QB_B to a high level.

The third reset circuit 240 is configured to reset the second node Q2 and the second output signal terminal OP2 under the control of the level of the sixth node QB_B. For example, the third reset circuit 240 is connected to the second node Q2, the sixth node QB_B, and the second output signal terminal OP2, and is configured to receive the first voltage and the fifth voltage VGL2. For example, when the third reset circuit 240 is turned on under the control of the level of the sixth node QB_B, the second node Q2 may be pulled down and reset using the first voltage, and the second output signal terminal OP2 may also be pulled down and reset using the fifth voltage VGL2. It should be noted that, in some embodiments of the present disclosure, the second output signal terminal OP2 may also be pulled down and reset using the first voltage, which is not limited in the present disclosure.

The fourth reset circuit 250 is configured to reset the second node Q2 and the second output signal terminal OP2 under the control of the level of the fifth node QB_A. For example, the fourth reset circuit 250 is connected to the second node Q2, the fifth node QB_A, and the second output signal terminal OP2, and is configured to receive the first voltage and the fifth voltage VGL2. For example, when the fourth reset circuit 250 is turned on under the control of the level of the fifth node QB_A, the second node Q2 may be pulled down and reset using the first voltage, and the second output signal terminal OP2 may also be pulled down and reset using the fifth voltage VGL2.

It should be noted that, in the embodiments of the present disclosure, for example, the third voltage VDD_A and the fourth voltage VDD_B may be configured to be inverted phase signals to each other, that is, when the third voltage VDD_A is at a high level, the fourth voltage VDD_B is at a low level, and when the third voltage VDD_A is at a low level, the fourth voltage VDD_B is at a high level. In this way, only one of the first control circuit 130 and the second control circuit 230 is in the working state at the same time, which can avoid the performance drift caused by the circuit working for a long time, thereby improving the stability of the circuit.

It should be noted that in the embodiments of the present disclosure, each node (the first node Q1, the second node Q2, the third node H, the fourth node N, the fifth node QB_A, the sixth node QB_B, etc.) and each output terminal (the shift signal output terminal CRT, the first output signal terminal OP1, the second output signal terminal OP2, etc.) are all provided for a better description of the circuit structure, and do not indicate actual components. A node represents a meeting point of related circuit connections in a circuit structure, that is, the related circuits connected to the same node are electrically connected to each other. For example, as illustrated in FIG. 10, the first control circuit 130, the first reset circuit 140, and the fourth reset circuit 250 are all connected to the fifth node QB_A, which means that these circuits are electrically connected to each other.

As illustrated in FIG. 11, in the shift register units 10 provided by some embodiments of the present disclosure, the first sub-unit 100 further includes a third control circuit 160, a fourth control circuit 170, and a common control circuit; the second sub-unit 200 further includes a fifth control circuit 260 and a sixth control circuit 270.

The third control circuit 160 is connected to the fifth node QB_A and a common control node CC, and is configured to, in response to the first clock signal CLKA, enable the fifth node QB_A to be electrically connected to the common control node CC.

The common control circuit 161 is electrically connected to the common control node CC and the first voltage terminal VGL1, and is configured to, under the control of the level of the third node H, enable the common control node CC to be electrically connected to the first voltage terminal VGL1.

The fifth control circuit 260 is connected to the sixth node QB_B and the common control node CC, and is configured to, in response to the first clock signal CLKA, enable the sixth node QB_B to be electrically connected to the common control node CC.

For example, in the blanking period of one frame, when the first clock signal CLKA is at a high level and the third node H is at a high level, the third control circuit 160, the common control circuit 161, and the fifth control circuit 260 are all turned on, so that the fifth node QB_A is electrically connected to the first voltage terminal VGL1 through the third control circuit 160 and the common control circuit 161, and the low-level first voltage may pull down the fifth node QB_A; the sixth node QB_B is electrically connected to the first voltage terminal VGL1 through the fifth control circuit 260 and the common control circuit 161, so that the low-level first voltage may pull down the sixth node QB_B. That is, the common control circuit 161 is used to control both the level of the fifth node QB_A and the level of the sixth node QB_B, so that the circuit structure may be simplified.

As illustrated in FIG. 12, some embodiments of the present disclosure further provide a shift register unit 10. The following describes only the differences between the shift register unit 10 illustrated in FIG. 12 and the shift register unit 10 illustrated in FIG. 11, and the similarities will not be repeated here.

As illustrated in FIG. 12, the third control circuit 160 is connected to the third node H, the fifth node QB_A, and the common control node CC, and is configured to, under the control of the third node H, enable the fifth node QB_A to be electrically connected to the common control node CC.

The common control circuit 161 is electrically connected to the common control node CC and the first voltage terminal VGL1, and is configured to, in response to the first clock signal CLKA, enable the common control node CC to be electrically connected to the first voltage terminal VGL1.

The fifth control circuit 260 is connected to the third node H, the sixth node QB_B, and the common control node CC, and is configured to, under the control of the level of the third node H, enable the sixth node QB_B to be electrically connected to the common control node CC.

For example, in the blanking period of one frame, when the first clock signal CLKA is at a high level and the third node H is at a high level, the third control circuit 160, the common control circuit 161, and the fifth control circuit 260 are all turned on, so that the fifth node QB_A is electrically connected to the first voltage terminal VGL1 through the third control circuit 160 and the common control circuit 161, and the low-level first voltage may pull down the fifth node QB_A; the sixth node QB_B is electrically connected to the first voltage terminal VGL1 through the fifth control circuit 260 and the common control circuit 161, so that the low-level first voltage may pull down the sixth node QB_B. That is, the common control circuit 161 is used to control both the level of the fifth node QB_A and the level of the sixth node QB_B, so that the circuit structure may be simplified.

As illustrated in FIG. 11 and FIG. 12, the fourth control circuit 170 is electrically connected to the fifth node QB_A and the first voltage terminal VGL1, and is configured to control the level of the fifth node QB_A in response to the first input signal STU1. For example, in the display period of one frame, the fourth control circuit 170 is turned on in response to the first input signal STU1, thereby pulling down the fifth node QB_A using the low-level first voltage. Pulling the fifth node QB_A to a low potential can avoid the influence of the fifth node QB_A on the first node Q1, thereby enabling the first node Q1 to be charged more sufficiently in the display period.

The sixth control circuit 270 is electrically connected to the sixth node QB_B and the first voltage terminal VGL1, and is configured to control the level of the sixth node QB_B in response to the first input signal STU1. For example, in the display period of one frame, the sixth control circuit 270 is turned on in response to the first input signal STU1, thereby pulling down the sixth node QB_B using the low-level first voltage. Pulling down the sixth node QB_B to a low potential can avoid the influence of the sixth node QB_B on the second node Q2, thereby enabling the second node Q2 to be charged more sufficiently in the display period.

As illustrated in FIG. 11 and FIG. 12, the first sub-unit 100 further includes a fifth reset circuit 180 and a sixth reset circuit 190, and the second sub-unit 200 further includes a seventh reset circuit 280 and an eighth reset circuit 290.

The fifth reset circuit 180 is connected to the first node Q1 and the leakage prevention node OF, and is configured to reset the first node Q1 in response to the display reset signal STD; the sixth reset circuit 190 is connected to the first node Q1 and the leakage prevention node OF, and is configured to reset the first node Q1 in response to the total reset signal TRST.

As can be seen from the above description, when the first node Q1 is at a high level, the second leakage prevention sub-circuit 420 remains turned on. For example, in the display period of one frame, the fifth reset circuit 180 is turned on in response to the display reset signal STD, so that the first node Q1 is electrically connected to the first voltage terminal VGL1 through the fifth reset circuit 180 and the second leakage prevention sub-circuit 420, and the first node Q1 may be pulled down and reset using the low-level first voltage. For example, in the case where a plurality of shift register units 10 are cascaded to form the gate driving circuit, the shift register unit 10 of a certain stage may receive the shift signal CR output by the shift register unit 10 of other stage as the display reset signal STD.

For example, in the case where a plurality of shift register units 10 are cascaded to form the gate driving circuit, before the display period of one frame, the sixth reset circuit 190 in each stage of the shift register unit 10 is turned on in response to the total reset signal TRST, so that the first node Q1 is electrically connected to the first voltage terminal VGL1 through the sixth reset circuit 190 and the second leakage prevention sub-circuit 420, and the first node Q1 may be pulled down and reset using the low-level first voltage.

As described above, in the shift register units 10 provided by some embodiments of the present disclosure, the fifth reset circuit 180 and the sixth reset circuit 190 are both connected to the leakage prevention node OF, in the case where the fifth reset circuit 180 or the sixth reset circuit 190 needs to perform a reset operation on the first node Q1, the second leakage prevention sub-circuit 420 may be multiplexed. In addition, the leakage prevention circuit 400 may also prevent the first node Q1 from leaking through the fifth reset circuit 180 or the sixth reset circuit 190. That is, the second leakage prevention sub-circuit 420 can implement both leakage prevention and the reset operation of the first node Q1, thereby simplifying the circuit structure.

As illustrated in FIG. 11 and FIG. 12, the seventh reset circuit 280 is connected to the second node Q2 and the leakage prevention node OF, and is configured to reset the second node Q2 in response to the display reset signal STD; the eighth reset circuit 290 is connected to the second node Q2 and the leakage prevention node OF, and is configured to reset the second node Q2 in response to the total reset signal TRST.

For example, in the display period of one frame, the seventh reset circuit 280 is turned on in response to the display reset signal STD, so that the second node Q2 is electrically connected to the first voltage terminal VGL1 through the seventh reset circuit 280 and the second leakage prevention sub-circuit 420, and the second node Q2 may be pulled down and reset using the low-level first voltage.

For example, in the case where a plurality of shift register units 10 are cascaded to form the gate driving circuit, before the display period of one frame, the eighth reset circuit 290 in each stage of the shift register unit 10 is turned on in response to the total reset signal TRST, so that the second node Q2 is electrically connected to the first voltage terminal VGL1 through the eighth reset circuit 290 and the second leakage prevention sub-circuit 420, and the second node Q2 may be pulled down and reset using the low-level first voltage.

As described above, in the shift register units 10 provided by some embodiments of the present disclosure, the seventh reset circuit 280 and the eighth reset circuit 290 are both connected to the leakage prevention node OF, and in the case where the seventh reset circuit 280 or the eighth reset circuit 290 needs to perform a reset operation on the second node Q2, the second leakage prevention sub-circuit 420 may be multiplexed. In addition, the leakage prevention circuit 400 may also prevent the second node Q2 from leaking through the seventh reset circuit 280 or the eighth reset circuit 290. That is, the second leakage prevention sub-circuit 420 can implement both leakage prevention and the reset operation of the second node Q2, thereby simplifying the circuit structure.

It should be understood by those skilled in the art that although a plurality of control circuits and a plurality of reset circuits are illustrated in FIG. 11 and FIG. 12, the above examples do not limit the protection scope of the present disclosure. In a practical application, those skilled in the art can select one or more of the above circuits according to a situation, and various combinations based on the above various circuits are not deviated from the principle of the present disclosure. Details are not described herein again.

In some embodiments of the present disclosure, the shift register unit 10 may be implemented as the circuit structure illustrated in FIG. 13. As illustrated in FIG. 13, the shift register unit 10 includes a first sub-unit 100 and a leakage prevention circuit 400. The first sub-unit 100 includes a first input circuit 110, a first output circuit 120, a first control circuit 130, a first reset circuit 140, a fourth control circuit 170, a fifth reset circuit 180, and a sixth reset circuit 190.

As illustrated in FIG. 13, the first input circuit 110 may be implemented as a first input transistor B1. The gate electrode of the first input transistor B1 is configured to receive the first input signal STU1, the first electrode of the first input transistor B1 is configured to receive the first voltage VDD, the second electrode of the first input transistor B1 is connected to the first node Q1.

For example, in another example, as illustrated in FIG. 14A, the gate electrode of the first input transistor B1 is connected to the first electrode of the first input transistor B1, and is configured to receive the first input signal STU1, so that when the first input signal STU1 is at a high level, the first node Q1 may be charged using the high-level first input signal STU1.

For example, in yet another example, as illustrated in FIG. 14B, the first input circuit 110 further includes a second input transistor B2. The gate electrode of the second input transistor B2 and the first electrode of the second input transistor B2 are connected to the second electrode of the first input transistor B1, and the second electrode of the second input transistor B2 is connected to the first node Q1. Because the second input transistor B2 adopts a diode connection, current may only flow from the first electrode of the second input transistor B2 to the second electrode of the second input transistor B2, but not from the second electrode (that is, the first node Q1) of the second input transistor B2 to the first electrode of the second input transistor B2, so that leakage of the first node Q1 can be avoided.

For example, in yet another example, as illustrated in FIG. 14C, the gate electrode of the second input transistor B2 is connected to the gate electrode of the first input transistor B1, the gate electrode of the second input transistor B2 and the gate electrode of the first input transistor B1 are both configured to receive the first input signal STU1, and the first electrode of the second input transistor B2 is electrically connected to the leakage prevention node OF. The first input circuit 110 illustrated in FIG. 14C can avoid the leakage of the first node Q1 by being connected to the leakage prevention node OF.

As illustrated in FIG. 13, the first output circuit 120 may include a first output transistor D1, a second output transistor D2, and a second capacitor C2. The gate electrode of the first output transistor D1 is connected to the first node Q1, the first electrode of the first output transistor D1 is configured to receive the second clock signal CLKB as the shift signal CR, the second electrode of the first output transistor D1 is connected to the shift signal output terminal CRT, and is configured to output the shift signal CR.

The gate electrode of the second output transistor D2 is connected to the first node Q1, the first electrode of the second output transistor D2 is configured to receive the third clock signal CLKC as the first output signal OUT1, and the second electrode of the second output transistor D2 It is connected to the first output signal terminal OP1, and is configured to output the first output signal OUT1. The first electrode of the second capacitor C2 is connected to the first node Q1, and the second electrode of the second capacitor C2 is connected to the second electrode of the second output transistor D2 (that is, the first output signal terminal OP1).

As illustrated in FIG. 13, the first control circuit 130 may be implemented to include a ninth control transistor E9 and a tenth control transistor E10. The gate electrode and the first electrode of the ninth control transistor E9 are configured to receive the third voltage VDD_A, and the second electrode of the ninth control transistor E9 is connected to the fifth node QB_A. The gate electrode of the tenth control transistor E10 is connected to the first node Q1, the first electrode of the tenth control transistor E10 is connected to the fifth node QB_A, and the second electrode of the tenth control transistor E10 is configured to be connected to the first voltage terminal VGL1 to receive the first voltage.

As illustrated in FIG. 13, the first reset circuit 140 may be implemented to include a seventh reset transistor R7, an eighth reset transistor R8, and a ninth reset transistor R9.

The gate electrode of the seventh reset transistor R7 is connected to the fifth node QB_A, the first electrode of the seventh reset transistor R7 is connected to the first node Q1, and the second electrode of the seventh reset transistor R7 is connected to the leakage prevention node OF. The gate electrode of the eighth reset transistor R8 is connected to the fifth node QB_A, the first electrode of the eighth reset transistor R8 is connected to the shift signal output terminal CRT, and the second electrode of the eighth reset transistor R8 is connected to the first voltage terminal VGL1 to receive the first voltage. The gate electrode of the ninth reset transistor R9 is connected to the fifth node QB_A, the first electrode of the ninth reset transistor R9 is connected to the first output signal terminal OP1, and the second electrode of the ninth reset transistor R9 is configured to receive the fifth voltage VGL2.

As illustrated in FIG. 13, the fourth control circuit 170 may be implemented as a second control transistor E2. The gate electrode of the second control transistor E2 is configured to receive the first input signal STU1, the first electrode of the second control transistor E2 is connected to the fifth node QB_A, and the second electrode of the second control transistor E2 is connected to the first voltage terminal VGL1 to receive the first voltage.

As illustrated in FIG. 13, the fifth reset circuit 180 may be implemented as a first reset transistor R1, and the sixth reset circuit 190 may be implemented as a second reset transistor R2. The gate electrode of the first reset transistor R1 is configured to receive the display reset signal STD, the first electrode of the first reset transistor R1 is connected to the first node Q1, and the second electrode of the first reset transistor R1 is connected to the leakage prevention node OF. The gate electrode of the second reset transistor R2 is configured to receive the total reset signal TRST, the first electrode of the second reset transistor R2 is connected to the first node Q1, and the second electrode of the second reset transistor R2 is connected to the leakage prevention node OF.

It should be noted that, for the descriptions of the first leakage prevention transistor A1 and the second leakage prevention transistor A2, reference may be made to the corresponding descriptions in FIG. 3, and details are not described here.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 15. The following describes only the differences between the shift register unit 10 illustrated in FIG. 15 and the shift register unit 10 illustrated in FIG. 13, and the similarities will not be repeated here.

As illustrated in FIG. 15, the first input circuit 110 includes a first input transistor B1 and a second input transistor B2, that is, the first input circuit 110 adopts the circuit structure illustrated in FIG. 14C.

As illustrated in FIG. 15, the shift register unit 10 further includes a thirteenth control transistor E13 and a fourteenth control transistor E14. The gate electrode and the first electrode of the thirteenth control transistor E13 are configured to receive the fourth voltage VDD_B, and the second electrode of the thirteenth control transistor E13 is connected to the sixth node QB_B. The gate electrode of the fourteenth control transistor E14 is connected to the first node Q1, the first electrode of the fourteenth control transistor E14 is connected to the sixth node QB_B, and the second electrode of the fourteenth control transistor E14 is configured to be connect to the first voltage terminal VGL1 to receive the first voltage.

It should be noted that, in the embodiments of the present disclosure, for example, the third voltage VDD_A and the fourth voltage VDD_B may be configured to be inverted phase signals to each other, that is, when the third voltage VDD_A is at a high level, the fourth voltage VDD_B is at a low level, and when the third voltage VDD_A is at a low level, the fourth voltage VDD_B is at a high level. In this way, only one of the ninth control transistor E9 and the thirteenth control transistor E13 is in the working state at the same time, which can avoid the performance drift caused by the transistor working for a long time, thereby improving the stability of the circuit.

As illustrated in FIG. 15, the shift register unit 10 further includes a fifth control transistor E5. The gate electrode of the fifth control transistor E5 is configured to receive the first input signal STU1, the first electrode of the fifth control transistor E5 is connected to the sixth node QB_B, and the second electrode of the fifth control transistor E5 is connected to the first voltage terminal VGL1 to receive the first voltage.

As illustrated in FIG. 15, in order to cooperate with the sixth node QB_B, the shift register unit 10 further includes a tenth reset transistor R10, an eleventh reset transistor R11, and a twelfth reset transistor R12.

The gate electrode of the tenth reset transistor R10 is connected to the sixth node QB_B, the first electrode of the tenth reset transistor R10 is connected to the first node Q1, and the second electrode of the tenth reset transistor R10 is connected to the leakage prevention node OF. The gate electrode of the eleventh reset transistor R11 is connected to the sixth node QB_B, the first electrode of the eleventh reset transistor R11 is connected to the shift signal output terminal CRT, and the second electrode of the eleventh reset transistor R11 is connected to the first voltage terminal VGL1 to receive the first voltage. The gate electrode of the twelfth reset transistor R12 is connected to the sixth node QB_B, the first electrode of the twelfth reset transistor R12 is connected to the first output signal terminal OP1, and the second electrode of the twelfth reset transistor R12 is configured to receive the fifth voltage VGL2.

In some embodiments of the present disclosure, the shift register unit 10 illustrated in FIG. 11 may be implemented as the circuit structure illustrated in FIG. 16. As illustrated in FIG. 16, the shift register unit 10 includes a first sub-unit 100, a second sub-unit 200, and a leakage prevention circuit 400. The first sub-unit 100 includes a first input circuit 110, a first output circuit 120, a first control circuit 130, a third control circuit 160, a common control circuit 161, a fourth control circuit 170, a first reset circuit 140, a second reset circuit 150, a fifth reset circuit 180, and a sixth reset circuit 190. The second sub-unit 200 includes a second input circuit 210, a second output circuit 220, a second control circuit 230, a fifth control circuit 260, a sixth control circuit 270, a third reset circuit 240, a fourth reset circuit 250, a seventh reset circuit 280, and an eighth reset circuit 290.

As illustrated in FIG. 16, the first input circuit 110 includes a first input transistor B1 and a second input transistor B2. The first output circuit 120 includes a first output transistor D1, a second output transistor D2, and a second capacitor C2. The first reset circuit 140 includes a seventh reset transistor R7, an eighth reset transistor R8, and a ninth reset transistor R9. The fourth control circuit 170 includes a second control transistor E2. For the descriptions of the first input transistor B1, the second input transistor B2, the first output transistor D1, the second output transistor D2, the second capacitor C2, the seventh reset transistor R7, the eighth reset transistor R8, the ninth reset transistor R9, and the second control transistor E2, reference may be made to the corresponding descriptions in the embodiment illustrated in FIG. 13, and details are not described here.

As illustrated in FIG. 16, the second input circuit 210 includes a third input transistor B3 and a fourth input transistor B4. The second output circuit 220 includes a third output transistor D3 and a third capacitor C3.

The gate electrode of the third input transistor B3 is configured to receive the first input signal STU1, the first electrode of the third input transistor B3 is connected to the leakage prevention node OF, and the second electrode of the third input transistor M3 is connected to the second node Q2. The gate electrode of the fourth input transistor B4 is connected to the first electrode of the fourth input transistor B4, and is configured to receive the first input signal STU1, and the second electrode of the fourth input transistor B4 is connected to the leakage prevention node OF.

The gate electrode of the third output transistor D3 is connected to the second node Q2, the first electrode of the third output transistor D3 is configured to receive the fourth clock signal CLKD as the second output signal OUT2, and the second electrode of the third output transistor D3 is connected to the second output signal terminal OP2, and is configured to output the second output signal OUT2. The first electrode of the third capacitor C3 is connected to the second node Q2, and the second electrode of the third capacitor C3 is connected to the second electrode of the third output transistor D3 (that is, the second output signal terminal OP2).

As illustrated in FIG. 16, the first control circuit 130 includes a ninth control transistor E9, a tenth control transistor E10, an eleventh control transistor E11, and a twelfth control transistor E12. The gate electrode and the first electrode of the ninth control transistor E9 are configured to receive the third voltage VDD_A, and the second electrode of the ninth control transistor E9 is connected to the first electrode of the tenth control transistor E10. The gate electrode of the tenth control transistor E10 is connected to the first node Q1, and the second electrode of the tenth control transistor E10 is configured to receive the sixth voltage VGL3. The gate electrode of the eleventh control transistor E11 is connected to the second electrode of the ninth control transistor E9, the first electrode of the eleventh control transistor E11 is configured to receive the third voltage VDD_A, and the second electrode of the eleventh control transistor E11 is connected to the fifth node QB_A. The gate electrode of the twelfth control transistor E12 is connected to the first node Q1, the first electrode of the twelfth control transistor E12 is connected to the fifth node QB_A, and the second electrode of the twelfth control transistor E12 is connected to the first voltage terminal VGL1 to receive the first voltage.

In the embodiments of the present disclosure, the sixth voltage VGL3 is, for example, at a low level, and the following embodiments are the same and will not be repeated. In the embodiments of the present disclosure, the sixth voltage VGL3 may be the same as or different from the first voltage.

As illustrated in FIG. 16, the second control circuit 230 includes a thirteenth control transistor E13, a fourteenth control transistor E14, a fifteenth control transistor E15, and a sixteenth control transistor E16. The gate electrode and the first electrode of the thirteenth control transistor E13 are configured to receive the fourth voltage VDD_B, and the second electrode of the thirteenth control transistor E13 is connected to the first electrode of the fourteenth control transistor E14. The gate electrode of the fourteenth control transistor E14 is connected to the second node Q2, and the second electrode of the fourteenth control transistor E14 is configured to receive the sixth voltage VGL3. The gate electrode of the fifteenth control transistor E15 is connected to the second electrode of the thirteenth control transistor E13, the first electrode of the fifteenth control transistor E15 is configured to receive the fourth voltage VDD_B, and the second electrode of the fifteenth control transistor E15 is connected to the sixth node QB_B. The gate electrode of the sixteenth control transistor E16 is connected to the second node Q2, the first electrode of the sixteenth control transistor E16 is connected to the sixth node QB_B, and the second electrode of the sixteenth control transistor E16 is connected to the first voltage terminal VGL1 to receive the first voltage.

As illustrated in FIG. 16, the third control circuit 160 includes a first control transistor E1, the fourth control circuit 170 includes a second control transistor E2, and the common control circuit 161 includes a third control transistor E3.

The gate electrode of the first control transistor E1 is configured to receive the first clock signal CLKA, the first electrode of the first control transistor E1 is connected to the fifth node QB_A, and the second electrode of the first control transistor E1 is connected to the common control node CC.

The gate electrode of the second control transistor E2 is configured to receive the first input signal STU1, the first electrode of the second control transistor E2 is connected to the fifth node QB_A, and the second electrode of the second control transistor E2 is connected to the first voltage terminal VGL1.

The gate electrode of the third control transistor E3 is connected to the third node H, the first electrode of the third control transistor E3 is connected to the common control node CC, and the second electrode of the third control transistor E3 is connected to the first voltage terminal VGL1.

As illustrated in FIG. 16, the fifth control circuit 260 includes a fourth control transistor E4, and the sixth control circuit 270 includes a fifth control transistor E5.

The gate electrode of the fourth control transistor E4 is configured to receive the first clock signal CLKA, the first electrode of the fourth control transistor E4 is connected to the sixth node QB_B, and the second electrode of the fourth control transistor E4 is connected to the common control node CC.

The gate electrode of the fifth control transistor E5 is configured to receive the first input signal STU1, the first electrode of the fifth control transistor E5 is connected to the sixth node QB_B, and the second electrode of the fifth control transistor E5 is connected to the first voltage terminal VGL1.

In the shift register units 10 provided by some embodiments of the present disclosure, the third control transistor E3 may be multiplexed by providing the common control node CC, so that the circuit structure may be simplified.

As illustrated in FIG. 16, the second reset circuit 150 includes a tenth reset transistor R10, an eleventh reset transistor R11, and a twelfth reset transistor R12.

The gate electrode of the tenth reset transistor R10 is connected to the sixth node QB_B, the first electrode of the tenth reset transistor R10 is connected to the first node Q1, and the second electrode of the tenth reset transistor R10 is connected to the leakage prevention node OF. The gate electrode of the eleventh reset transistor R11 is connected to the sixth node QB_B, the first electrode of the eleventh reset transistor R11 is connected to the shift signal output terminal CRT, and the second electrode of the eleventh reset transistor R11 is connected to the first voltage terminal VGL1 to receive the first voltage. The gate electrode of the twelfth reset transistor R12 is connected to the sixth node QB_B, the first electrode of the twelfth reset transistor R12 is connected to the first output signal terminal OP1, and the second electrode of the twelfth reset transistor R12 is configured to receive the fifth voltage VGL2.

As illustrated in FIG. 16, the third reset circuit 240 includes a thirteenth reset transistor R13 and a fourteenth reset transistor R14. The fourth reset circuit 250 includes a fifteenth reset transistor R15 and a sixteenth reset transistor R16.

The gate electrode of the thirteenth reset transistor R13 is connected to the sixth node QB_B, the first electrode of the thirteenth reset transistor R13 is connected to the second node Q2, and the second electrode of the thirteenth reset transistor R13 is connected to the leakage prevention node OF. The gate electrode of the fourteenth reset transistor R14 is connected to the sixth node QB_B, the first electrode of the fourteenth reset transistor R14 is connected to the second output signal terminal OP2, and the second electrode of the fourteenth reset transistor R14 is configured to receive the fifth voltage VGL2. The gate electrode of the fifteenth reset transistor R15 is connected to the fifth node QB_A, the first electrode of the fifteenth reset transistor R15 is connected to the second node Q2, and the second electrode of the fifteenth reset transistor R15 is connected to the leakage prevention node OF. The gate electrode of the sixteenth reset transistor R16 is connected to the fifth node QB_A, the first electrode of the sixteenth reset transistor R16 is connected to the second output signal terminal OP2, and the second electrode of the sixteenth reset transistor R16 is configured to receive the fifth voltage VGL2.

As illustrated in FIG. 16, the fifth reset circuit 180 includes a first reset transistor R1 and a fifth reset transistor R5, and the seventh reset circuit 280 includes a third reset transistor R3.

The gate electrode of the first reset transistor R1 is configured to receive the display reset signal STD, the first electrode of the first reset transistor R1 is connected to the first node Q1, and the second electrode of the first reset transistor R1 is connected to the leakage prevention node OF. The gate electrode of the fifth reset transistor R5 is configured to receive the display reset signal STD, the first electrode of the fifth reset transistor R5 is connected to the leakage prevention node OF, and the second electrode of the fifth reset transistor R5 is connected to the first voltage terminal VGL1 to receive the first voltage. The gate electrode of the third reset transistor R3 is configured to receive the display reset signal STD, the first electrode of the third reset transistor R3 is connected to the second node Q2, and the second electrode of the third reset transistor R3 is connected to the leakage prevention node OF.

In the shift register units 10 provided by some embodiments of the present disclosure, connecting the first reset transistor R1 to the leakage prevention node OF may prevent the first node Q1 from leaking through the first reset transistor RE Similarly, connecting the third reset transistor R3 to the leakage prevention node OF may prevent the second node Q2 from leaking through the third reset transistor R3. In addition, when resetting the first node Q1 and the second node Q2, the fifth reset transistor R5 may be multiplexed, so that the circuit structure of the shift register unit 10 may be simplified.

As illustrated in FIG. 16, the sixth reset circuit 190 includes a second reset transistor R2 and a sixth reset transistor R6, and the eighth reset circuit 290 includes a fourth reset transistor R4.

The gate electrode of the second reset transistor R2 is configured to receive the total reset signal TRST, the first electrode of the second reset transistor R2 is connected to the first node Q1, and the second electrode of the second reset transistor R2 is connected to the leakage prevention node OF. The gate electrode of the sixth reset transistor R6 is configured to receive the total reset signal TRST, the first electrode of the sixth reset transistor R6 is connected to the leakage prevention node OF, and the second electrode of the sixth reset transistor R6 is connected to the first voltage terminal VGL1 to receive the first voltage. The gate electrode of the fourth reset transistor R4 is configured to receive the total reset signal TRST, the first electrode of the fourth reset transistor R4 is connected to the second node Q2, and the second electrode of the fourth reset transistor R4 is connected to the leakage prevention node OF.

In the shift register units 10 provided by some embodiments of the present disclosure, connecting the second reset transistor R2 to the leakage prevention node OF may prevent the first node Q1 from leaking through the second reset transistor R2. Similarly, connecting the fourth reset transistor R4 to the leakage prevention node OF may prevent the second node Q2 from leaking through the fourth reset transistor R4. In addition, when resetting the first node Q1 and the second node Q2, the sixth reset transistor R6 may be multiplexed, so that the circuit structure of the shift register unit 10 may be simplified.

As illustrated in FIG. 16, the first leakage prevention sub-circuit 410 includes a first leakage prevention transistor A1, and the second leakage prevention sub-circuit 420 includes a second leakage prevention transistor A2.

The gate electrode of the first leakage prevention transistor A1 is connected to the first node Q1, the first electrode of the first leakage prevention transistor A1 is configured to receive the second voltage VDD, and the second electrode of the first leakage prevention transistor A1 is connected to the leakage prevention node OF.

The gate electrode and the first electrode of the second leakage prevention transistor A2 are configured to be connected to the leakage prevention node OF, and the second electrode of the second leakage prevention transistor A2 is configured to be connected to the first voltage terminal VGL1 to receive the first voltage.

It should be noted that, for the descriptions of the blanking input sub-unit 300 in FIG. 16, reference may be made to the corresponding descriptions in FIG. 8, and FIG. 9A to FIG. 9D, and details are not described here.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 17. The following describes only the differences between the shift register unit 10 illustrated in FIG. 17 and the shift register unit 10 illustrated in FIG. 16, and the similarities will not be repeated here.

As illustrated in FIG. 17, the second input circuit 210 includes only the third input transistor B3 and does not include the fourth input transistor B4. For example, the first input signal STU1 may charge the first node Q1 through the first input transistor B1 and the second input transistor B2, and the first input signal STU1 may charge the second node Q2 through the first input transistor B1 and the third input transistor B3, that is, when charging the first node Q1 and the second node Q2, the first input transistor B1 is multiplexed, so that one transistor may be saved, and the circuit structure of the shift register unit 10 is further simplified.

As illustrated in FIG. 17, the fifth reset circuit 180 includes only the first reset transistor R1 and does not include the fifth reset transistor R5. For example, when the display reset signal STD is at a high level, the reset operation on the first node Q1 may be performed by the first reset transistor R1 and the second leakage prevention transistor A2; in addition, the reset operation on the second node Q2 may be performed by the third reset transistor R3 and the second leakage prevention transistor A2. That is, when resetting the first node Q1 and the second node Q2, the second leakage prevention transistor A2 is multiplexed, so that one transistor may be saved, and the circuit structure of the shift register unit 10 is further simplified.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 18. The following describes only the differences between the shift register unit 10 illustrated in FIG. 18 and the shift register unit 10 illustrated in FIG. 17, and the similarities will not be repeated here.

As illustrated in FIG. 18, the second leakage prevention sub-circuit 420 includes a third leakage prevention transistor A3. The gate electrode of the third leakage prevention transistor A3 is connected to the first node Q1 or the second node Q2, the first electrode of the third leakage prevention transistor A3 is connected to the leakage prevention node OF, and the second electrode of the third leakage prevention transistor A3 is connected to the first voltage terminal VGL1 to receive the first voltage.

Different from other embodiments, in the embodiment illustrated in FIG. 18, the second leakage prevention sub-circuit 420 does not adopt a diode connection. For example, when the first node Q1 or the second node Q2 is at a high level, the third leakage prevention transistor A3 is turned on, so that a conductive path is formed between the leakage prevention node OF and the first voltage terminal VGL1, and the level of the leakage prevention node OF is greater than the first voltage provided by the first voltage terminal VGL1.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 19. The following describes only the differences between the shift register unit 10 illustrated in FIG. 19 and the shift register unit 10 illustrated in FIG. 17, and the similarities will not be repeated here.

As illustrated in FIG. 19, in the shift register unit 10, the third control circuit 160 includes a sixth control transistor E6, the common control circuit 161 includes a seventh control transistor E7, and the fifth control circuit 260 includes an eighth control transistor E8.

The gate electrode of the sixth control transistor E6 is connected to the third node H, the first electrode of the sixth control transistor E6 is connected to the fifth node QB_A, and the second electrode of the sixth control transistor E6 is connected to the common control node CC.

The gate electrode of the seventh control transistor E7 is configured to receive the first clock signal CLKA, the first electrode of the seventh control transistor E7 is connected to the common control node CC, and the second electrode of the seventh control transistor E7 is connected to the first voltage terminal VGL1.

The gate electrode of the eighth control transistor E8 is connected to the third node H, the first electrode of the eighth control transistor E8 is connected to the sixth node QB_B, and the second electrode of the eighth control transistor E8 is connected to the common control node CC.

In the shift register unit 10 illustrated in FIG. 19, the seventh control transistor E7 may be multiplexed by providing the common control node CC, so that the circuit structure may be simplified.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 20. The following describes only the differences between the shift register unit 10 illustrated in FIG. 20 and the shift register unit 10 illustrated in FIG. 16, and the similarities will not be repeated here.

As illustrated in FIG. 20, the fifth reset circuit 180 includes only the first reset transistor R1 and does not include the fifth reset transistor R5. The sixth reset circuit 190 includes only the second reset transistor R2 and does not include the sixth reset transistor R6. Therefore, the number of transistors may be saved, and the circuit structure may be simplified.

In some embodiments of the present disclosure, the shift register unit 10 may also be implemented as the circuit structure illustrated in FIG. 21. The following describes only the differences between the shift register unit 10 illustrated in FIG. 21 and the shift register unit 10 illustrated in FIG. 20, and the similarities will not be repeated here.

As illustrated in FIG. 21, the second input circuit 210 includes only the third input transistor B3 and does not include the fourth input transistor B4, thereby further saving the number of transistors and further simplifying the circuit structure.

The shift register units provided by the embodiments of the present disclosure can avoid the leakage of the first node Q1 and the second node Q2, and avoid the problem of poor display of the display device adopting the shift register unit. In addition, the circuit structure may be simplified, so that the bezel size of the display device adopting the shift register unit may be reduced, and the PPI of the display device may be improved.

As described above, in the shift register units 10 provided by the embodiments of the present disclosure, the level of the third node H may be maintained by the first capacitor C1, the level of the first node Q1 may be maintained by the second capacitor C2, and the level of the second node Q2 may be maintained by the third capacitor C3. The first capacitor C1, the second capacitor C2, and the third capacitor C3 may be the capacitor component fabricated by a manufacturing process, for example, by fabricating a dedicated capacitor electrode. Each electrode of the capacitor may be implemented through a metal layer, a semiconductor layer (e.g., doped polysilicon) and the like. And in some examples, by designing circuit wiring parameters enables that the first capacitor C1, the second capacitor C2, and the third capacitor C3 may also be implemented by parasitic capacitance between the various devices. The connection manner of the first capacitor C1, the second capacitor C2, and the third capacitor C3 is not limited to the manner described above, and may be other suitable connection manners as long as the levels provided to the third node H, the first node Q1, and the second node Q2 can be stored.

Some embodiments of the present disclosure further provide a gate driving circuit 20, as illustrated in FIG. 22, the gate driving circuit 20 includes a plurality of cascaded shift register units 10, and any one or more shift register units 10 may adopt the structure or variant of the shift register unit 10 provided by the embodiment of the present disclosure. A1, A2, A3, A4, A5, and A6 in FIG. 22 represent sub-units in the shift register unit 10, for example, A1, A3, and A5 represent the first sub-units in three shift register units 10, respectively, and A2, A4 and A6 represent the second sub-units of the three shift register units 10, respectively.

For example, as illustrated in FIG. 22, each shift register unit 10 includes a first sub-unit and a second sub-unit to output the first output signal OUT1 and the second output signal OUT2, respectively. In the case where the gate driving circuit 20 is used to drive a display panel, the first output signal OUT1 and the second output signal OUT2 may respectively drive a row of sub-pixel units in the display panel. For example, A1, A2, A3, A4, A5, and A6 may respectively drive the first row, the second row, the third row, the fourth row, the fifth row, and the sixth row of sub-pixel units in the display panel.

The gate driving circuit 20 provided by the embodiment of the present disclosure may share the blanking input sub-unit, so that the bezel size of the display device adopting the gate driving circuit may be reduced, and the PPI of the display device may be improved. In addition, the random compensation may also be implemented, thereby avoiding the problems of poor display such as the scanning lines and the uneven display brightness due to the progressive sequence compensation.

Next, taking the gate driving circuit 20 illustrated in FIG. 22 as an example, the signal lines in the gate driving circuit 20 are described.

As illustrated in FIG. 22, the gate driving circuit 20 includes a first sub-clock signal line CLK_1, a second sub-clock signal line CLK_2, and a third sub-clock signal line CLK_3. The first sub-unit in the (3n-2)th-stage shift register unit is connected to the first sub-clock signal line CLK_1 to receive the second clock signal CLKB of the (3n-2)th-stage shift register unit; the first sub-unit in the (3n-1)th-stage shift register unit is connected to the second sub-clock signal line CLK_2 to receive the second clock signal CLKB of the (3n-1)th-stage shift register unit; the first sub-unit in the (3n)th-stage shift register unit is connected to the third sub-clock signal line CLK_3 to receive the second clock signal CLKB of the (3n)th-stage shift register unit; and n is an integer greater than zero.

As described above, in the case where the shift register units 10 are cascaded, it is only necessary to sequentially provide the second clock signal CLKB to the first sub-unit in each stage of the shift register unit 10, and the second clock signal CLKB may be output as the shift signal CR to complete the shift of the scanning.

As illustrated in FIG. 22, the gate driving circuit 20 further includes a fourth sub-clock signal line CLK_4, a fifth sub-clock signal line CLK_5, a sixth sub-clock signal line CLK_6, a seventh sub-clock signal line CLK_7, an eighth sub-clock signal Line CLK_8, and a ninth sub-clock signal line CLK_9.

The first sub-unit in the (3n-2)th-stage shift register unit is connected to the fourth sub-clock signal line CLK_4 to receive the third clock signal CLKC of the (3n-2)th-stage shift register unit, and the second sub-unit in the (3n-2)th-stage shift register unit is connected to the fifth sub-clock signal line CLK_5 to receive the fourth clock signal CLKD of the (3n-2)th-stage shift register unit.

The first sub-unit in the (3n-1)th-stage shift register unit is connected to the sixth sub-clock signal line CLK_6 to receive the third clock signal CLKC of the (3n-1)th-stage shift register unit, and the second sub-unit in the (3n-1)th-stage shift register unit is connected to the seventh sub-clock signal line CLK_7 to receive the fourth clock signal CLKD of the (3n-1)th-stage shift register unit.

The first sub-unit in the (3n)th-stage shift register unit is connected to the eighth sub-clock signal line CLK_8 to receive the third clock signal CLKC of the (3n)th-stage shift register unit, and the second sub-unit in the (3n)th-stage shift register unit is connected to the ninth sub-clock signal line CLK_9 to receive the fourth clock signal CLKD of the (3n)th-stage shift register unit.

As described above, the driving signals that are output row by row are provided to the shift register units 10 of all stages through a total of six clock signal lines including the fourth sub-clock signal line CLK_4, the fifth sub-clock signal line CLK_5, the sixth sub-clock signal line CLK_6, the seventh sub-clock signal line CLK_7, the eighth sub-clock signal line CLK_8, and the ninth sub-clock signal on the line CLK_9. That is, the gate driving circuit 20 provided by the embodiment of the present disclosure may adopt the clock signal of 6CLK, which may cause the waveforms of the driving signals output by the gate driving circuit 20 to overlap, for example, the pre-charge time of each row of sub-pixel units may be increased, so that the gate driving circuit may be suitable for a high-frequency display scanning. The embodiments of the present disclosure do not limit the types of the clock signals adopted, for example, the clock signals such as 8CLK and 10CLK may also be adopted.

As illustrated in FIG. 22, the gate driving circuit 20 further includes a tenth sub-clock signal line CLK_10, an eleventh sub-clock signal line CLK_11, and a twelfth sub-clock signal line CLK_12.

For example, the first sub-unit and the second sub-unit in each stage of the shift register unit 10 are both connected to the tenth sub-clock signal line CLK_10 to receive the total reset signal TRST. The selection control circuit 310 in each stage of the shift register unit 10 is connected to the eleventh sub-clock signal line CLK_11 to receive the selection control signal OE. The first sub-unit, the second sub-unit, and the third input circuit 320 in each stage of the shift register unit 10 are both connected to the twelfth sub-clock signal line CLK_12 to receive the first clock signal CLKA.

As illustrated in FIG. 22, the gate driving circuit 20 further includes a thirteenth sub-clock signal line CLK_13 and a fourteenth sub-clock signal line CLK_14.

For example, the first sub-unit in each stage of the shift register unit 10 is connected to the thirteenth sub-clock signal line CLK_13 to receive the third voltage VDD_A; the second sub-unit in each stage of the shift register unit 10 is connected to the fourteenth sub-clock signal line CLK_14 to receive the fourth voltage VDD_B.

As illustrated in FIG. 22, the gate driving circuit 20 further includes a fifteenth sub-clock signal line CLK_15, and the first sub-unit and the second sub-unit in the first-stage shift register unit 10 is connected to the fifteenth sub-clock signal line CLK_15 to receive the first input signal STU1.

As illustrated in FIG. 22, except the first-stage shift register unit 10, the first sub-unit and the second sub-unit in the shift register unit 10 of other stage are connected to the first sub-unit in the shift register unit 10 of a preceding stage, which is before the shift register unit 10 of other stage, to receive the shift signal CR as the first input signal STU1. Except the shift register units 10 of the last two stages, the first sub-unit and the second sub-unit in the shift register unit 10 of other stage are connected to the first sub-unit in the shift register unit 10 of a next second stage, which is after the shift register unit 10 of other stage, to receive the shift signal CR as the display reset signal STD.

It should be noted that the cascaded relationship illustrated in FIG. 22 is only an example, and according to the descriptions of the present disclosure, other cascaded manners may also be adopted according to actual conditions.

For example, in an example, the shift register unit 10 in the gate driving circuit 20 illustrated in FIG. 22 may adopt the circuit structure illustrated in FIG. 21, and FIG. 23 illustrates the signal timing diagram corresponding to the operation of the gate driving circuit illustrated in FIG. 22.

In FIG. 23, H<5> represents the third node H in the third-stage shift register unit 10, and the third-stage shift register unit 10 corresponds to the fifth row and the sixth row of the sub-pixel units in the display panel. N<5> represents the fourth node N in the third-stage shift register unit 10.

Q1<1> and Q2<2> respectively represent the first node Q1 and the second node Q2 in the first-stage shift register unit 10; Q1<5> and Q2<6> respectively represent the first node Q1 and the second node Q2 in the third-stage shift register unit 10. The number in parenthesis indicates the number of the row of the sub-pixel units in the display panel corresponding to the node, and the following embodiments are the same and will not be described in detail.

OUT1<1> and OUT2<2> respectively represent the first output signal OUT1 and the second output signal OUT2 output by the first-stage shift register unit 10. Similarly, OUT1<3> and OUT2<4> respectively represent the first output signal OUT1 and the second output signal OUT2 output by the second-stage shift register unit 10; and OUT1<5> and OUT2<6> respectively represent the first output signal OUT1 and the second output signal OUT2 output by the third-stage shift register unit 10. CR<1>, CR<3>, and CR<5> respectively represent the shift signals CR output by the first-stage shift register unit 10, the second-stage shift register unit 10, and the third-stage shift register unit 10. For example, as illustrated in FIG. 23, CR<1> and OUT1<1> are the same, CR<3> and OUT1<3> are the same, and CR<5> and OUT1<5> are the same.

1F represents the first frame, DS represents the display period in the first frame, and BL represents the blanking period in the first frame. In addition, it should be noted that, FIG. 23 is illustrated by taking the third voltage VDD_A as a low level and the fourth voltage VDD_B as a high level as an example, but the embodiments of the present disclosure are not limited thereto. The levels of signals in the signal timing diagram illustrated in FIG. 23 is only schematic and do not represent the true level value.

The working principle of the gate driving circuit 20 illustrated in FIG. 22 is described below with reference to the signal timing diagram in FIG. 23 and the shift register unit 10 illustrated in FIG. 21.

Before the start of the first frame 1F, the tenth sub-clock signal line CLK_10 and the eleventh sub-clock signal line CLK_11 provide high levels, the second reset transistor R2 and the fourth reset transistor R4 in each stage of the shift register unit 10 are turned on, so that the first node Q1 and the second node Q2 in each stage of the shift register unit 10 may be reset; the fifth input transistor B5 and the sixth input transistor B6 in each stage of the shift register unit 10 are turned on, because the second input signal STU2 received at this time is at a low level, the third node H in each stage of the shift register unit 10 may be reset, so that the total reset may be implemented before the start of the first frame 1F.

In the display period DS of the first frame 1F, the working process for the third-stage shift register unit 10 (that is, corresponding to the fifth and sixth rows of the sub-pixel units in the display panel) is described as follows.

In the first stage 1, the shift signal CR<3> output by the first sub-unit in the second-stage shift register unit 10 is at a high level, that is, the first input signal STU1 received by the third-stage shift register unit 10 is at a high level, so the first input transistor B1, the second input transistor B2, and the third input transistor B3 are turned on. The high-level first input signal STU1 charges the first node Q1<5> through the first input transistor B1 and the second input transistor B2, thereby pulling up the first node Q1<5> to a high level; the high-level first input signal STU1 may also charge the second node Q2<6> through the first input transistor B1 and the third input transistor B3, thereby pulling up the second node Q2<6> to a high level.

The second output transistor D2 is turned on under the control of the first node Q1<5>, but because the third clock signal CLKC provided by the eighth sub-clock signal line CLK_8 is at a low level at this time, the first output signal OUT1<5> output by the third-stage shift register unit 10 is at a low level; the third output transistor D3 is turned on under the control of the second node Q2<6>, but because the fourth clock signal CLKD provided by the ninth sub-clock signal line CLK_9 is at a low level at this time, so the second output signal OUT2<6> output by the third-stage shift register unit 10 is at a low level; in this stage, the first node and the second node in the third-stage shift register unit 10 are simultaneously pre-charged.

In the second stage 2, the third clock signal CLKC provided by the eighth sub-clock signal line CLK_8 becomes a high level, and the potential of the first node Q1<5> is further pulled up due to the bootstrap effect, so the second output transistor D2 remains turned on, so that the first output signal OUT1<5> output by the third-stage shift register unit 10 becomes a high level. However, because the fourth clock signal CLKD provided by the ninth sub-clock signal line CLK_9 is still at a low level at this time, the second output signal OUT2<6> output by the third-stage shift register unit 10 continues to remain at a low level.

In the third stage 3, the fourth clock signal CLKD provided by the ninth sub-clock signal line CLK_9 becomes a high level, the potential of the second node Q2<6> is further pulled up due to the bootstrap effect, and the third output transistor D3 remains turned on, so that the second output signal OUT2<6> output by the third-stage shift register unit 10 becomes a high level.

In the fourth stage 4, due to the holding effect of the second capacitor C2, the first node Q1<5> still maintains a high level, so the second output transistor D2 is turned on. However, because the third clock signal CLKC provided by the eighth sub-clock signal line CLK_8 becomes a low level, the first output signal OUT1<5> output by the third-stage shift register unit 10 becomes a low level. In addition, due to the bootstrap effect of the second capacitor C2, the potential of the first node Q1<5> also drops.

In the fifth stage 5, due to the holding effect of the third capacitor C3, the second node Q2<6> still maintains a high level, so the third output transistor D3 is turned on. However, because the fourth clock signal CLKD provided by the ninth sub-clock signal line CLK_9 becomes a high level, the second output signal OUT2<6> output by the third-stage shift register unit 10 becomes a low level. In addition, due to the bootstrap effect of the third capacitor C3, the potential of the second node Q2<6> also drops.

In the sixth stage 6, because the clock signal of 6CLK is adopted, the signals output by each three stages of the shift register units 10 (each stage sequentially outputs the first output signal OUT1 and the second output signal OUT2) are a cycle, and because the third-stage shift register unit 10 receives the shift signal CR output by the fifth-stage shift register unit 10 as the display reset signal STD, so in this stage when the third clock signal CLKC provided by the sixth sub-clock signal line CLK_6 becomes a high level, the display reset signal STD received by the third-stage shift register unit 10 is also at a high level, so that the first reset transistor R1 and the third reset transistor R3 are turned on, and the first node Q1<5> and the second node Q2<6> are pulled down and reset using the low-level first voltage.

The third-stage shift register unit 10 drives the fifth and sixth rows of the sub-pixels in the display panel to complete the display, accordingly, the fourth-stage shift register unit 10, the fifth-stage shift register units and the like progressively drive the sub-pixel units in the display panel to complete the display driving of one frame. Here, the display period of the first frame ends.

Moreover, the third node H is also charged in the display period DS of the first frame 1F. For example, in the case where the fifth row of sub-pixel units needs to be compensated in the first frame 1F, then the following operations are further performed in the display period DS of the first frame 1F.

In the second stage 2 and the third stage 3, the eleventh sub-clock signal line CLK_11 is provided with the same signal as the shift signal CR<5> output from the third-stage shift register unit 10, so the fifth input transistor B5 and the sixth input transistor B6 are turned on. In addition, the second input signal STU2 received by the third-stage shift register unit 10 may be made to be the same as the shift signal CR<5>, so that the high-level second input signal STU2 may charge the third node H<5>, and the third node H<5> is pulled up to a high level.

It should be noted that the above charging process for the third node H<5> is only an example, and the embodiments of the present disclosure include but are not limited to this. For example, the second input signal STU2 received by the third-stage shift register unit 10 may also be the same as the shift signal CR output by the shift register unit 10 of other stage, while making the signal provided to the eleventh sub-clock signal line CLK_11 has the same signal timing as the second input signal STU2.

The high potential of the third node H<5> may be maintained until the blanking period BL of the first frame 1F. In the case where the fifth row of sub-pixel units needs to be compensated in the first frame 1F, the following operations are performed in the blanking period BL of the first frame 1F.

In the seventh stage 7, the first clock signal CLKA provided by the twelfth sub-clock signal line CLK_12 is at a high level. Because the third node H<5> remains at a high level in this stage, the seventh input transistor B7 is turned on, the high-level first clock signal CLKA is transmitted to the fourth node N<5> through the seventh input transistor B7, so that the fourth node N<5> becomes a high level. The first transmission transistor T1, the second transmission transistor T2, and the third transmission transistor T3 are turned on under the control of the high-level first clock signal CLKA, so the high-level first clock signal CLKA may charge the first node Q1<5> and the second node Q2<6>, respectively, and the levels of the first node Q1<5> and the second node Q2<6> are pulled up.

In addition, in the seventh stage 7, due to the coupling effect of the first capacitor C1, the fourth node N<5> pulls up, by coupling, the third node H<5> when the fourth node N<5> changes from a low level to a high level, so that the third node H<5> may be kept at a higher high potential to ensure that the seventh input transistor B7 is fully turned on.

Then the first clock signal CLKA provided by the twelfth sub-clock signal line CLK_12 changes from a high level to a low level, so that the fourth node N<5> becomes a low level, due to the coupling effect of the first capacitor C1 the potential of the third node H<5> also drops.

In the eighth stage 8, the third clock signal CLKC provided by the eighth sub-clock signal line CLK_8 becomes a high level, the potential of the first node Q1<5> is further pulled up due to the bootstrap effect, so the second output transistor D2 remains turned on, so that the first output signal OUT1<5> output by the third-stage shift register unit 10 becomes a high level. However, because the fourth clock signal CLKD provided by the ninth sub-clock signal line CLK_9 is still at a low level, the second output signal OUT2<6> output by the third-stage shift register unit 10 is at a low level.

For example, the first output signal OUT1<5> output in the eighth stage 8 may be used to drive the sensing transistors in the sub-pixel units in the display panel to implement the external compensation.

In the ninth stage 9, due to the holding effect of the second capacitor C2, the first node Q1<5> still maintains a high level, so the second output transistor D2 is turned on. However, because the third clock signal CLKC provided by the eighth sub-clock signal line CLK_8 becomes a low level, the first output signal OUT1<5> output by the third-stage shift register unit 10 becomes a low level. In addition, due to the bootstrap effect of the second capacitor C2, the potential of the first node Q1<5> also drops.

In the tenth stage 10, the tenth sub-clock signal line CLK_10 and the eleventh sub-clock signal line CLK_11 provide high levels, the second reset transistor R2 and the fourth reset transistor R4 in each stage of the shift register unit 10 are turned on, so that the first node Q1 and the second node Q2 in each stage of the shift register unit 10 may be reset; the fifth input transistor B5 and the sixth input transistor B6 in each stage of the shift register unit 10 are turned on, because the second input signal STU2 received at this time is at a low level, the third node H in each stage of the shift register unit 10 may be reset to complete the total reset.

Here, the driving timing of the first frame 1F ends. The driving method of the gate driving circuit in the subsequent stages such as in the second frame, the third frame, and the like may be with reference to the above description, and details are not described herein again.

It should be noted that, the above descriptions of the working principle of the random compensation is described by taking the case where the driving signal corresponding to the fifth row of the sub-pixel units of the display panel is output during the blanking period of the first frame as an example, which is not limited in the present disclosure. For example, in the case where the driving signal corresponding to the (n)th row of the sub-pixel units of the display panel needs to be output during the blanking period of a frame, the corresponding third node H needs to be pulled up to a high level during the display period DS of the frame, in addition, in the blanking period BL of the frame, the high-level first clock signal CLKA is provided to pull up the potential of the first node Q1 or the second node Q2, and then when it is necessary to output a high-level driving signal, the high-level third clock signal CLKC or fourth clock signal CLKD is provided, n is an integer greater than zero.

In addition, in the embodiments of the present disclosure, the same timing of two signals refers to time synchronization at a high level, and does not require that the two signals have the same amplitude.

Some embodiments of the present disclosure further provide a gate driving circuit 20, as illustrated in FIG. 24, and FIG. 25 is a signal timing diagram corresponding to the operation of the gate driving circuit illustrated in FIG. 24. The differences between the gate driving circuit 20 illustrated in FIG. 24 and the gate driving circuit 20 illustrated in FIG. 22 are described below.

As illustrated in FIG. 24 and FIG. 25, in the present embodiment, the gate driving circuit 20 adopts the clock signal of 10CLK, and the driving signals that are output row by row are provided to the shift register units 10 of all stages through a total of ten clock signal lines including the fourth sub-clock signal line CLK_4, the fifth sub-clock signal line CLK_5, the sixth sub-clock signal line CLK_6, the seventh sub-clock signal line CLK_7, the eighth sub-clock signal line CLK_8, the ninth sub-clock signal line CLK_9, the fifteenth sub-clock signal line CLK_15, the sixteenth sub-clock signal line CLK_16, the seventeenth sub-clock signal line CLK_17, and the eighteenth sub-clock signal line CLK_18. In the embodiment of the present disclosure, the clock signal of 10CLK may be used to further increase the pre-charge time of each row of sub-pixel units, so that the gate driving circuit may be suitable for the display scanning with a higher frequency.

In the embodiments illustrated in FIG. 24 and FIG. 25, except the shift register units 10 of the first two stages, the shift register unit 10 of other stage is connected to the first sub-unit in the shift register unit 10 of a preceding second stage, which is before the shift register unit 10 of other stage, to receive the shift signal CR as the first input signal STU1. Except the shift register units 10 of the last four stages, the shift register unit 10 of other stage is connected to the first sub-unit in the shift register unit 10 of a next fourth stage, which is after the shift register unit 10 of other stage, to receive the shift signal CR as the display reset signal STD.

As illustrated in FIG. 24, the tenth sub-clock signal line CLK_10 is connected to the first sub-units and the second sub-units (that is, A1, A2, A3, and A4) in the shift register units 10 of the first two stages to provide the first input signal STU1, and the tenth sub-clock signal line CLK_10 is further connected to the shift register units 10 of other stages to provide the total reset signal TRST. In this way, the number of the clock signal lines may be saved, so that the bezel size of the display device adopting the gate driving circuit may be reduced, and the PPI of the display device may be improved.

As illustrated in FIG. 25, for example, in the present embodiment, it is selected to compensate the eleventh row of the sub-pixel units (corresponding to the sixth-stage shift register unit 10). In the display period DS of the first frame 1F, the third node H<11> is charged; in the blanking period BL, the high-level first clock signal CLKA is provided to complete the charging of the first node Q1<11> and the second node Q2<12>, and then the fourth sub-clock signal line CLK_4 provides a high-level third clock signal, so that the first output signal OUT1<11> output by the sixth-stage shift register unit 10 is at a high level, and the first output signal OUT1<11> may be used to drive the eleventh row of the sub-pixel units to complete the external compensation.

Some embodiments of the present disclosure further provide a display device 1, as illustrated in FIG. 26, the display device 1 includes the gate driving circuit 20 provided by the embodiment of the present disclosure, and a plurality of sub-pixel units 510 arranged in an array. For example, the display device 1 further includes a display panel 50, and the pixel array composed of the plurality of sub-pixel units 510 is disposed in the display panel 50.

The first output signal OUT1 and the second output signal OUT2 output by each shift register unit 10 in the gate driving circuit 20 are respectively provided to the sub-pixel units 510 in different rows, for example, the gate driving circuit 20 is electrically connected to the sub-pixel units 510 through the gate lines GL. The gate driving circuit 20 is used to provide the driving signals to the pixel array, for example, the driving signals may drive the scanning transistors and the sensing transistors in the sub-pixel units 510.

For example, the display device 1 may further include a data driving circuit 30 for providing data signals to the pixel array. For example, the data driving circuit 30 is electrically connected to the sub-pixel units 510 through the data lines DL.

It should be noted that the display device 1 in the present embodiments may be: a liquid crystal panel, a liquid crystal television, a display screen, an OLED panel, an OLED television, an electronic paper display device, a mobile phone, a tablet computer, a notebook computer, a digital photo frame, a navigator, or any product or component with the display function.

The technical effects of the display device 1 provided by the embodiments of the present disclosure can be with reference to the corresponding description of the gate driving circuit 20 in the above embodiments, and details are not described herein again.

Some embodiments of the present disclosure further provide a driving method that may be used to drive the shift register unit 10 provided by the embodiment of the present disclosure, a plurality of the shift register units 10 may be cascaded to form the gate driving circuit provided by an embodiment of the present disclosure, and the gate driving circuit is used to drive the display panel to display at least one frame of pictures.

The driving method includes: causing the leakage prevention circuit 400 to control the level of the leakage prevention node OF under the control of the level of the first node Q1, causing the conductive path to be formed between the leakage prevention node OF and the first voltage terminal VGL1, and causing the circuit connected between the first node Q1 and the leakage prevention node OF to be turned off.

It should be noted that the detailed description and technical effects of the driving method provided by the embodiments of the present disclosure may be with reference to the description of the working principle of the shift register unit 10 and the gate driving circuit 20 in the embodiments of the present disclosure, and details are not described herein again.

What have been described above are only specific implementations of the present disclosure, the protection scope of the present disclosure is not limited thereto, and the protection scope of the present disclosure should be based on the protection scope of the claims. 

What is claimed is:
 1. A shift register unit, comprising a first sub-unit and a leakage prevention circuit, and the first sub-unit comprises a first input circuit, a first output circuit, a blanking input sub-unit and a second sub-unit, wherein the first input circuit is configured to control a level of a first node in response to a first input signal, the first output circuit is configured to provide an output signal at an output terminal under control of the level of the first node, and the leakage prevention circuit is connected to the first node and a first voltage terminal, and is configured to control a level of a leakage prevention node under control of the level of the first node, so as to form a conductive path between the leakage prevention node and the first voltage terminal and turn off a circuit connected between the first node and the leakage prevention node, wherein the leakage prevention circuit comprises a first leakage prevention sub-circuit and a second leakage prevention sub-circuit, the first leakage prevention sub-circuit is connected to the first node and the leakage prevention node, and is configured to control the level of the leakage prevention node under control of the level of the first node, and the second leakage prevention sub-circuit is connected to the leakage prevention node and the first voltage terminal, and the second leakage prevention sub-circuit is configured to form the conductive path between the leakage prevention node and the first voltage terminal under control of the level of the leakage prevention node or the level of the first node, the blanking input sub-unit is connected to the first node, and is configured to receive a selection control signal and control the level of the first node; the second sub-unit comprises a second input circuit and a second output circuit, the second input circuit is configured to control a level of a second node in response to the first input signal, and the second output circuit is configured to output a second output signal under control of the level of the second node, and wherein the second output signal of the second output circuit and the first output signal of the first output circuit correspond to a same stage of the shift register unit, and the second output signal of the second output circuit is used for compensating a row of sub-pixel units during a blanking period of one frame.
 2. The shift register unit according to claim 1, wherein the first leakage prevention sub-circuit comprises a first leakage prevention transistor, and the second leakage prevention sub-circuit comprises a second leakage prevention transistor; a gate electrode of the first leakage prevention transistor is connected to the first node, a first electrode of the first leakage prevention transistor is configured to receive a second voltage, and a second electrode of the first leakage prevention transistor is connected to the leakage prevention node; and a gate electrode of the second leakage prevention transistor and a first electrode of the second leakage prevention transistor are configured to be connected to the leakage prevention node, and a second electrode of the second leakage prevention transistor is configured to be connected to the first voltage terminal.
 3. The shift register unit according to claim 1, wherein the first leakage prevention sub-circuit comprises a first leakage prevention transistor, and the second leakage prevention sub-circuit comprises a third leakage prevention transistor; a gate electrode of the first leakage prevention transistor is connected to the first node, a first electrode of the first leakage prevention transistor is configured to receive a second voltage, and a second electrode of the first leakage prevention transistor is connected to the leakage prevention node; and a gate electrode of the third leakage prevention transistor is connected to the first node, a first electrode of the third leakage prevention transistor is connected to the leakage prevention node, and a second electrode of the third leakage prevention transistor is configured to be connected to the first voltage terminal.
 4. The shift register unit according to claim 1, wherein the blanking input sub-unit comprises a selection control circuit, a third input circuit, and a first transmission circuit; the selection control circuit is configured to control a level of a third node using a second input signal in response to the selection control signal, and maintain the level of the third node; the third input circuit is configured to transmit a first clock signal to a fourth node under control of the level of the third node; and the first transmission circuit is electrically connected to the first node, the fourth node, and the leakage prevention node, and is configured to control the level of the first node and the level of the leakage prevention node in respond to the first clock signal.
 5. The shift register unit according to claim 4, wherein the blanking input sub-unit further comprises a second transmission circuit, and the second transmission circuit is electrically connected to the second node and the leakage prevention node, and is configured to transmit the level of the leakage prevention node to the second node in respond to the first clock signal.
 6. The shift register unit according to claim 5, wherein the first transmission circuit comprises a first transmission transistor and a second transmission transistor, and the second transmission circuit comprises a third transmission transistor; a gate electrode of the first transmission transistor is configured to receive the first clock signal, a first electrode of the first transmission transistor is connected to the fourth node, and a second electrode of the first transmission transistor is connected to the leakage prevention node; a gate electrode of the second transmission transistor is configured to receive the first clock signal, a first electrode of the second transmission transistor is connected to the leakage prevention node, and a second electrode of the second transmission transistor is connected to the first node; and a gate electrode of the third transmission transistor is configured to receive the first clock signal, a first electrode of the third transmission transistor is connected to the leakage prevention node, and a second electrode of the third transmission transistor is connected to the second node.
 7. The shift register unit according to claim 5, wherein the first input circuit comprises a first input transistor and a second input transistor, and the second input circuit comprises a third input transistor; a gate electrode of the first input transistor and a first electrode of the first input transistor are configured to receive the first input signal, and a second electrode of the first input transistor is connected to the leakage prevention node; a gate electrode of the second input transistor is configured to receive the first input signal, a first electrode of the second input transistor is connected to the leakage prevention node, and a second electrode of the second input transistor is connected to the first node; and a gate electrode of the third input transistor is configured to receive the first input signal, a first electrode of the third input transistor is connected to the leakage prevention node, and a second electrode of the third input transistor is connected to the second node.
 8. The shift register unit according to claim 7, wherein the second input circuit further comprises a fourth input transistor, a gate electrode of the fourth input transistor and a first electrode of the fourth input transistor are configured to receive the first input signal, and a second electrode of the fourth input transistor is connected to the leakage prevention node.
 9. The shift register unit according to claim 5, wherein the first sub-unit further comprises a first control circuit, a first reset circuit, a second reset circuit, a shift signal output terminal, and a first output signal terminal; the second sub-unit further comprises a second control circuit, a third reset circuit, a fourth reset circuit, and a second output signal terminal; the output signal comprises a shift signal and a first output signal, the output terminal comprises the shift signal output terminal and the first output signal terminal, the shift signal output terminal is configured to output the shift signal, and the first output signal terminal is configured to output the first output signal; the second output signal terminal is configured to output the second output signal; the first control circuit is configured to control a level of a fifth node under control of both the level of the first node and a third voltage; the first reset circuit is configured to reset the first node, the shift signal output terminal, and the first output signal terminal under control of the level of the fifth node; the second reset circuit is configured to reset the first node, the shift signal output terminal, and the first output signal terminal under control of a level of a sixth node; the second control circuit is configured to control the level of the sixth node under control of both the level of the second node and a fourth voltage; the third reset circuit is configured to reset the second node and the second output signal terminal under control of the level of the sixth node; and the fourth reset circuit is configured to reset the second node and the second output signal terminal under control of the level of the fifth node.
 10. The shift register unit according to claim 9, wherein the first sub-unit further comprises a third control circuit, a fourth control circuit, and a common control circuit, and the second sub-unit further comprises a fifth control circuit and a sixth control circuit; the third control circuit is connected to the fifth node and a common control node, and is configured to, in response to the first clock signal, enable the fifth node to be electrically connected to the common control node; the common control circuit is electrically connected to the common control node and the first voltage terminal, and is configured to, under control of the level of the third node, enable the common control node to be electrically connected to the first voltage terminal; the fourth control circuit is electrically connected to the fifth node and the first voltage terminal, and is configured to control the level of the fifth node in response to the first input signal; the fifth control circuit is connected to the sixth node and the common control node, and is configured to, in response to the first clock signal, enable the sixth node is electrically connect to the common control node; and the sixth control circuit is electrically connected to the sixth node and the first voltage terminal, and is configured to control the level of the sixth node in response to the first input signal.
 11. The shift register unit according to claim 10, wherein the third control circuit comprises a first control transistor, the fourth control circuit comprises a second control transistor, the common control circuit comprises a third control transistor, the fifth control circuit comprises a fourth control transistor, and the sixth control circuit comprises a fifth control transistor; a gate electrode of the first control transistor is configured to receive the first clock signal, a first electrode of the first control transistor is connected to the fifth node, and a second electrode of the first control transistor is connected to the common control node; a gate electrode of the second control transistor is configured to receive the first input signal, a first electrode of the second control transistor is connected to the fifth node, and a second electrode of the second control transistor is connected to the first voltage terminal; a gate electrode of the third control transistor is connected to the third node, a first electrode of the third control transistor is connected to the common control node, and a second electrode of the third control transistor is connected to the first voltage terminal; a gate electrode of the fourth control transistor is configured to receive the first clock signal, a first electrode of the fourth control transistor is connected to the sixth node, and a second electrode of the fourth control transistor is connected to the common control node; and a gate electrode of the fifth control transistor is configured to receive the first input signal, a first electrode of the fifth control transistor is connected to the sixth node, and a second electrode of the fifth control transistor is connected to the first voltage terminal.
 12. The shift register unit according to claim 9, wherein the first sub-unit further comprises a third control circuit, a fourth control circuit, and a common control circuit, and the second sub-unit further comprises a fifth control circuit and a sixth control circuit; the third control circuit is connected to the third node, the fifth node, and a common control node, and is configured to, under control of the level of the third node, enable the fifth node to be electrically connected to the common control node; the common control circuit is electrically connected to the common control node and the first voltage terminal, and is configured to, in response to the first clock signal, enable the common control node to be electrically connected to the first voltage terminal; the fourth control circuit is electrically connected to the fifth node and the first voltage terminal, and is configured to control the level of the fifth node in response to the first input signal; the fifth control circuit is connected to the third node, the sixth node, and the common control node, and is configured to, under control of the level of the third node, enable the sixth node is electrically connect to the common control node; and the sixth control circuit is electrically connected to the sixth node and the first voltage terminal, and is configured to control the level of the sixth node in response to the first input signal.
 13. The shift register unit according to claim 12, wherein the third control circuit comprises a sixth control transistor, the fourth control circuit comprises a second control transistor, the common control circuit comprises a seventh control transistor, the fifth control circuit comprises an eighth control transistor, and the sixth control circuit comprises a fifth control transistor; a gate electrode of the sixth control transistor is connected to the third node, a first electrode of the sixth control transistor is connected to the fifth node, and a second electrode of the sixth control transistor is connected to the common control node; a gate electrode of the second control transistor is configured to receive the first input signal, a first electrode of the second control transistor is connected to the fifth node, and a second electrode of the second control transistor is connected to the first voltage terminal; a gate electrode of the seventh control transistor is configured to receive the first clock signal, a first electrode of the seventh control transistor is connected to the common control node, and a second electrode of the seventh control transistor is connected to the first voltage terminal; a gate electrode of the eighth control transistor is connected to the third node, a first electrode of the eighth control transistor is connected to the sixth node, and a second electrode of the eighth control transistor is connected to the common control node; and a gate electrode of the fifth control transistor is configured to receive the first input signal, a first electrode of the fifth control transistor is connected to the sixth node, and a second electrode of the fifth control transistor is connected to the first voltage terminal.
 14. The shift register unit according to claim 10, wherein the first sub-unit further comprises a fifth reset circuit and a sixth reset circuit, and the second sub-unit further comprises a seventh reset circuit and an eighth reset circuit; the fifth reset circuit is connected to the first node and the leakage prevention node, and is configured to reset the first node in response to a display reset signal, and the sixth reset circuit is connected to the first node and the leakage prevention node, and is configured to reset the first node in response to a total reset signal; and the seventh reset circuit is connected to the second node and the leakage prevention node, and is configured to reset the second node in response to the display reset signal, and the eighth reset circuit is connected to the second node and the leakage prevention node, and is configured to reset the second node in response to the total reset signal.
 15. The shift register unit according to claim 14, wherein the fifth reset circuit comprises a first reset transistor, the sixth reset circuit comprises a second reset transistor, the seventh reset circuit comprises a third reset transistor, and the eighth reset circuit comprises a fourth reset transistor; a gate electrode of the first reset transistor is configured to receive the display reset signal, a first electrode of the first reset transistor is connected to the first node, and a second electrode of the first reset transistor is connected to the leakage prevention node; a gate electrode of the second reset transistor is configured to receive the total reset signal, a first electrode of the second reset transistor is connected to the first node, and a second electrode of the second reset transistor is connected to the leakage prevention node; a gate electrode of the third reset transistor is configured to receive the display reset signal, a first electrode of the third reset transistor is connected to the second node, and a second electrode of the third reset transistor is connected to the leakage prevention node; and a gate electrode of the fourth reset transistor is configured to receive the total reset signal, a first electrode of the fourth reset transistor is connected to the second node, and a second electrode of the fourth reset transistor is connected to the leakage prevention node.
 16. A gate driving circuit, comprising a plurality of cascaded shift register units each of which is the shift register unit according to claim
 1. 17. A display device, comprising the gate driving circuit according to claim
 16. 18. A driving method for the shift register unit according to claim 1, comprising: causing the leakage prevention circuit to control the level of the leakage prevention node under control of the level of the first node, causing the conductive path to be formed between the leakage prevention node and the first voltage terminal, and causing the circuit connected between the first node and the leakage prevention node to be turned off. 